Noise Margin and Gate Delay. Debdeep Mukhpadhyay IIT Madras

Transcription

1 Noise Margin and Gate Delay Debdeep Mukhpadhyay IIT Madras

2 Logic levels Solid logic 0/1 defined by V SS /V DD. Inner bounds of logic values V L /V H are not directly determined by circuit properties, as in some other logic families. V DD V SS logic 1 unknown logic 0 V H V L

3 Logic level matching Levels at output of one gate must be sufficient to drive next gate.

4 Transfer characteristics Transfer curve shows static input/output relationship hold input voltage, measure output voltage.

5 Noise Margins How much noise can a gate input see before it does not recognize the input? Logical High Output Range Output Characteristics V DD V OH NM H Input Characteristics Logical High Input Range V IH V IL Indeterminate Region Logical Low Output Range V OL NM L GND Logical Low Input Range

6 Logic Levels To maximize noise margins, select logic levels at V out V DD β p /β n > 1 V in V out 0 V in V DD

7 Logic Levels To maximize noise margins, select logic levels at unity gain point of DC transfer characteristic V out V DD Unity Gain Points Slope = -1 V OH β p /β n > 1 V in V out V OL 0 V tn V IL V IH V DD - V tp V DD V in

8 Noise margin Noise margin = voltage difference between output of one gate and input of next. Noise must exceed noise margin to make second gate produce wrong output.

9 Delay Definitions t pdr : t pdf : t pd : t r : t f : fall time

10 Delay Definitions t pdr : rising propagation delay From input to rising output crossing V DD / t pdf : falling propagation delay From input to falling output crossing V DD / t pd : average propagation delay t pd = (t pdr + t pdf )/ t r : rise time From output crossing 0. V DD to 0.8 V DD t f : fall time From output crossing 0.8 V DD to 0. V DD

11 Delay Definitions t cdr : rising contamination delay From input to rising output crossing V DD / t cdf : falling contamination delay From input to falling output crossing V DD / t cd : average contamination delay t pd = (t cdr + t cdf )/

12 Simulated Inverter Delay Solving differential equations by hand is too hard SPICE simulator solves the equations numerically Uses more accurate I-V models too! But simulations take time to write (V) V in t pdf = 66ps t pdr = 83ps 0.5 V out p 400p 600p 800p 1n t(s)

13 Delay Estimation We would like to be able to easily estimate delay Not as accurate as simulation But can we give estimates? The step response usually looks like a 1 st order RC response with a decaying exponential. Use RC delay models to estimate delay C = total capacitance on output node Use effective resistance R So that t pd = RC Characterize transistors by finding their effective R Depends on average current as gate switches

14 RC delay Load is resistor + capacitor, driver is resistor. tf = 0.69 R CL For rise time replace by the PMOS resistance.

15 RC Delay Models Use equivalent circuits for MOS transistors Ideal switch + capacitance and ON resistance Unit nmos has resistance R, capacitance C Unit pmos has resistance R, capacitance C Capacitance proportional to width Resistance inversely proportional to width d kc R/k d d g k g g k g s kc kc s s s kc R/k kc kc d

16 Example: 3-input NAND Sketch a 3-input NAND with transistor widths chosen to achieve effective rise and fall resistances equal to a unit inverter (R).

17 Example: 3-input NAND Sketch a 3-input NAND with transistor widths chosen to achieve effective rise and fall resistances equal to a unit inverter (R)

18 3-input NAND Caps Annotate the 3-input NAND gate with gate and diffusion capacitance

19 3-input NAND Capacitors Annotate the 3-input NAND gate with gate and diffusion capacitance. C C C C C C C C C 3C 3C 3C C 3C 3C 3C

20 3-input NAND Capacitors Annotate the 3-input NAND gate with gate and diffusion capacitance. 5C 5C 5C C 3C 3C

21 Elmore Delay ON transistors look like resistors Pullup or pulldown network modeled as RC ladder Elmore delay of RC ladder t R C pd i to source i nodes i = R C + R + R C R + R R C ( ) ( ) R 1 R R 3 R N N N C 1 C C 3 C N

22 Example: -input NAND Estimate worst-case rising and falling delay of -input NAND driving h identical gates. Y A B x h copies

23 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B x 6C C Y 4hC h copies

24 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B R Y (6+4h)C x 6C C t pdr = Y 4hC h copies

25 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B x 6C C Y 4hC R Y (6+4h)C tpdr = 6+ 4h RC ( ) h copies

26 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B x 6C C Y 4hC h copies

27 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B x 6C C Y 4hC h copies R/ x R/ C Y (6+4h)C t pdf =

28 Example: -input NAND Estimate rising and falling propagation delays of a -input NAND driving h identical gates. A B x 6C C Y 4hC h copies R/ x R/ C Y (6+4h)C tpdf = C + + h C + ( )( R ) ( 6 4 ) ( R R ) = 7+ 4h RC ( )

29 Delay Components Delay has two parts Parasitic delay 6 or 7 RC Independent of load Effort delay 4h RC Proportional to load capacitance

30 CMOS inverter delay An approximate method: Assume constant I avg The NMOS and the PMOS are in saturated region and provide a constant current. t t PHL PLH = = k k n p C load ( V V ) C CC load ( V V ) CC V V CC Tn CC TP V 1 =Vcc V =½Vcc I 1 t 1 t I avg = I 1

31 Some Points The delay of a gate, be it the rise or the fall time is inversely proportional to VDD. Point to ponder: Effect of sizing on the inverter gate delay.