V. Transistor Amplifiers
|
|
- Roxanne Elisabeth Martin
- 7 years ago
- Views:
Transcription
1 V. Transstor Amplfers 5.1 Introducton In page 1-11, we showed that the response of a twoport networks n a system s completely determned f we sole the smple crcut shown. Furthermore, one can show that f a two-port network contans only lnear elements, the two-port network can be modeled wth a maxmum of four crcut elements. sg R sg 2port Network o For practcal crcut n whch the two-port network does not contan any ndependent sources, the two-port network can be modeled wth 3 elements: the nput resstance, the output resstance, and the oltage transfer functon as s shown below: As the combnaton of the two-port network and the load (dashed box n the crcut) s a two-termnal network, t can be modeled by ts Theenn equalent. Furthermore, as ths box does not contan an ndependent source, V T 0. As such, the box can be modeled as a resstor, called the nput resstance of the two-port network: Input Resstance: R Note that n general R depends on. sg R sg 2port Network o o 2port R L Network To fnd a model for the output port of a two-port network, we assume a oltage s drectly appled to the two-port network (.e., sg and R sg 0). In ths manner, the output port model wll be ndependent of R sg. Agan, as the box contanng and the two-port network s a two-termnal network, t can be modeled wth ts Theenn equalent (see Fgure). We call the Theenn resstance of ths box, the output resstance of the two-port network: Output Resstance: R o o 0 (Theenn Resstance) The Theenn oltage source, V T c the open-loop oltage alue. For an amplfer, the output oltage should be proportonal to. Therefore, f we defne Open-loop Gan: A o c RL ECE65 Lecture Notes (F. Najmabad), Sprng
2 Then, V T c A o,.e., the Theenn oltage can be modeled by a controlled oltage source. Combnng the models for the nput and output ports, we arre at the model for an amplfer whch conssts of three crcut elements as s shown below (left). R Ro A o o sg R sg R Ro A o o RL Voltage Amplfer Model The amplfer crcut model allows us to sole any amplfer confguraton once to compute the three parameters: A o, R and R o. We can then fnd the response of any crcut contanng ths amplfer by utlzng these three parameters (smlar to usng Theenn Theorem to label any two-termnal network wth R T and V T ). For example, for the generc two-port network crcut (crcut rght aboe), we can fnd the response of the amplfer to the presence of R sg and Load: A R o A o sg R R R sg sg sg R R R sg A R R R sg A o R o We see that the open-loop gan A o s the maxmum alue for the amplfer gan A. In addton, to maxmze / sg, we need R and R o 0. A practcal oltage amplfer, thus, s desgned to hae a large R and a small R o (.e., R R sg and R o ). A oltage-controlled oltage source s an deal oltage amplfer as R and R o 0. Smlarly, for a two-stage amplfer: sg R sg Ro1 Ro2 1 R 1 2 L 1 R R 2 A o1 1 A o2 2 o sg R 1 R 1 R sg A o1 R 2 R 2 R o1 A o2 R o2 Note that the nput resstance of the second amplfer, R 2, s the load for the frst amplfer and the output resstance of the frst amplfer, R o1 s R sg for the second one. ECE65 Lecture Notes (F. Najmabad), Sprng
3 We see that n order to maxmze the oltage gan, we need to ensure that the nput resstance of the frst stage s much larger than R sg, the output resstance of the last stage s much smaller than, and the nput resstance of any stage to be much larger than the output resstance of the preous stage: R,N R o,n1 as R of the N th stage appears as the load for N-1 th stage. For sngle-transstor amplfer confguratons (rest of ths secton), we wll see that s smpler to compute A (wth load present) drectly nstead of A o and R o separately. In ths case, the aboe formula for computng total gan of a two-stage amplfer can be smplfed to sg R 1 R 1 R sg A 1 ( R 2 ) A 2 ( ) where A 1 ( R 2 ) s the oltage gan wth R 2 beng the load, etc. An mportant cauton: In general, A o and R o are ndependent of both R sg and (why?). Howeer, R may depend on. Amplfer confguratons n whch R s ndependent of are called unlateral. It s easy, howeer, to ncorporate the dependence of R on by solng any mult-stage amplfer from the load sde toward the sgnal sde: In the aboe fgure, we know the fnal load whch can be used to compute R 2 and R 2 s the load for stage one and ges R 1. Analyss of Transstor Amplfer Crcuts Analyss of a transstor amplfer crcut follows these three steps as we need to address seeral ssues: bas, lnear response (to small sgnals) and the mpact of couplng capactors. Bas: Zero out the sgnal and replace capactors wth open crcuts. Analyze the crcut usng a large-sgnal model such as those of page 3-4 or 3-6 for BJT and 3-22/3-23 for MOS. Small Sgnal Response: 1) Compute, r o (and r π for BJT) from bas pont parameters 2) Zero out all bas sources 3) Assume capactors are short crcut. 4) Replace the transstor wth ts small sgnal model. 5) Inspect the crcut. If you dentfy the crcut as a prototype crcut, you can drectly use the formulas for that crcut. Otherwse sole for A, A o, R and R o. Frequency-response: Value of A found n the small sgnal response aboe s called the mdfrequency gan of the amplfer. Couplng and bypass capactors as well as the nternal capactance of transstors ntroduce poles both at low and hgh frequences. We wll ntroduce a method to compute the low-frequency poles. ECE102 nclude a more thorough reew of the amplfer frequency response. ECE65 Lecture Notes (F. Najmabad), Sprng
4 There are four fundamental sngle transstor amplfer confguratons possble and are examned n the followng sectons. Notes: 1) The small-sgnal models of PNP and NPN transstors (or PMOS and NMOS transstors) are smlar. Thus, the formulas dered below can be used for ether case. 2) The small-sgnal model of a BJT s smlar to that of a MOS wth the excepton of the addtonal resstor r π (the nput ports n a MOS s open crcut crcut). As such, we expect that formulas for MOS amplfers would be the same as those of BJT amplfer f we set r π. 3) For MOS crcuts, we use the common approxmaton r o 1 as 2I D V GS V tn, r o V A I D r o 2V A V GS V tn 1 typcally r o s 50 or more. 4) For BJT crcuts, we use the common approxmaton r o 1 as I C nv T, r o V A V CE I C V A I C r o V A V CE nv t 1 typcally r o s seeral thousands. In addton, r π β 1 5) In many text books (e.g., Sedra & Smth), the formulas for BJT amplfers are gen n terms of β & r e (nstead of & r π ) where r e 1 r π β wth r e typcally n 10s or 100 Ω range. Here we keep both form (so we can see the comparson to MOS amplfers) and also dere the formula n r e form. 6) Some manufacturer spec sheet for BJTs (e.g., spec sheet for 3N3904) use the older notaton (hybrd π model) for BJT whch are h fe β, h re r π, and h oe 1/r o ECE65 Lecture Notes (F. Najmabad), Sprng
5 5.2 Common-Dran and Common-Collector Amplfers Common-Dran or Source Follower Confguraton Crcut shown s the generc small-sgnal crcut of a common-dran amplfer (.e., we hae zeroed out all Bas sources). Note that the nput s appled at the gate and the output s taken at the source. As the dran s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common-dran amplfer. It s mportant to realze that as a transstor can be based n many ways, seeral complete crcuts (.e., ncludng the bas elements) wll reduce to the aboe small-sgnal form of a common-dran amplfer. Some examples are gen below. R G R S V DD R 1 V SS V DD R S o R 2 R S V DD V SS R G R 1 R 2 R G, R G, R S, no Pole from C1 no Pole from C1 We now proceed wth the small-sgnal analyss by replacng the MOS wth ts small-sgnal model. An mportant obseraton s that the resstor R S s parallel to and appears as the load for the transstor. In fact, n many applcatons, R S s replaced by the load (e.g. a speaker, nput of another amplfer crcut). As such, we defne R L R S. The openloop gan of the amplfer s calculated wth R L (both R S and are open crcut) and the output resstance s taken to the left of R S (see page 5-6) R G G gs _ S gs D r o R S R G gs G _ S g m gs r o R S D We compute, A (n the presence of a load) drectly as ths does not complcate the analyss. The open-loop gan s then calculated by settng. Inspectng the crcut, we fnd ECE65 Lecture Notes (F. Najmabad), Sprng
6 that the current gs wll flow n r o R L (from to the ground). Thus, gs Ohm Law: gs (r o R L) (r o R L)( ) A (r o R L ) 1 (r o R L) r o R L r o R L r o R L R L 1 R L where we hae used r o 1 to drop R L compared to r o R L n the denomnator. The open-loop gan can be fnd by settng R L to get r o R L r o and A o r o 1 r o 1 Because A o 1, S G and S follows the nput oltage. Thus, ths confguraton s also called the Source Follower. Fndng R s easy as R G (see crcut) and, therefore, R R G. As R s ndependent of, ths confguraton s unlateral. Note that f R G were not present (see example complete crcut of page 5-5), R. To fnd R o we need to zero out and compute the Theenn Equalent resstance seen at the output termnals. Because of the presence of the controlled source, we need to attach a x oltage source to the crcut and compute x : R G gs _ G S g m gs r o R L R G gs _ G S g m gs r o x x D R O D KCL: gs x x x gs x r o x r o 1 R o r o 1 1 r o r o R o s typcally small, a few 100 Ω. Note that: A A o 1 R o 1/ R L 1 R L whch s exactly the expresson we had dered before. ECE65 Lecture Notes (F. Najmabad), Sprng
7 In summary, the general propertes of the common-dran amplfer (source follower) nclude an open-loop oltage gan of unty, a large nput resstance (and can be made nfnte n some basng schemes) and a small output resstance. Ths type of crcut s typcally called a buffer and often used when there s a msmatch between nput resstance of one stage and the output resstance of the preous stage. Addtonally, L o as A o 1 but R R o. As such, ths crcut can be used to amplfy the sgnal current (and power) and dre a load (used typcally as the last stage of an amplfer crcut) Note re R o : In some text books (e.g., Sedra & Smth), the output resstance s defned to nclude R D (see crcut). If we call ths resstance to be R o, nspecton of the crcut shows that R o R D R o. R G gs _ G S D gs r o R O R D R O Common-Collector or Emtter Follower Confguraton Crcut shown s the generc small-sgnal crcut of a common-collector amplfer (.e., we hae zeroed out all Bas sources). Note that the nput s appled at the base and the output s taken at the emtter. As the collector s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common-collector amplfer. As can be seen ths confguraton s analogous to MOS common-dran. Smlarly to the MOS case, the BJT can be based many ways. Seeral complete crcuts (.e., ncludng the bas elements) wll reduce to the aboe small-sgnal form of a common-collector amplfer. Some examples are gen below. R B R E V EE R R 1 E C o 1 V CC V EE R 2 R E V EE V CC R G R 1 R 2 R G, R G, R S, no Pole from C1 no Pole from C1 Smlar to the common-dran confguraton, R E s parallel to and appears as the load for the transstor. We defne R L R E. and the output resstance s taken to the left of R E n the crcut aboe. Proceedng wth the small-sgnal analyss by replacng the BJT wth ts small-sgnal model: ECE65 Lecture Notes (F. Najmabad), Sprng
8 R B B π _ r π E π R E C r o R B B π _ E b r π π r o R E C Inspectng the crcut, we fnd that a total current of b π flows flow n r o R L (from to the ground) where b π /r π : π ( Ohm Law: A π π r π ) (r o R L ) π (r o R L ) (r o R L )( ) r o R L r o R L 1 r o R L r o R L r o R L A R L 1 R L R L R L r e A o r o 1 r o 1 where we hae used r π β 1 n the 2nd equaton to drop π /r π term, and r o 1 to drop R L n the denomnator of the 3rd equaton. Snce r e 1/ n typcally a few tens of Ohms, A 1 unless R L s ery small (tens of Ω). Ths confguraton s also called the Emtter Follower. as e b and e follows the nput oltage. To fnd R / (note r π β): KCL: R B b KVL: b r π ( b π )(r o ) b[r π (1 r π )(r o )] b R B R B r π (1 β)(r o ) R R B r π (1 β)(r o ) R R B [r π (1 β)(r o R L )] Snce R depends on, ths amplfer confguraton s NOT unlateral. Note that when emtter degeneraton basng s used, we need to hae R B (1 β)r E. In ths case, R R B (smlar to the common-dran amplfer n whch R R G ) and the ECE65 Lecture Notes (F. Najmabad), Sprng
9 confguraton becomes unlateral. If R B s not present, the nput resstance s large although t s not nfnte as s the case for the common-dran amplfer. To fnd R o we need to zero out and compute the Theenn Equalent resstance seen at the output termnals: R B B π _ E b r π π r o R L R B B π _ E b r π π r o x x C R O C Because of the presence of the controlled source, we need to attach x oltage source to the crcut and compute x. Notng that π x KCL: x π x x x x x r o r π 1/ r o r π 1 x R o (1/ ) r o r π (1/ ) r e R o x 1/ r o r π snce r π 1 and r o 1. If the output resstance s taken nclude R C, R o R C R o (smlar to the source follower, see fgure n page 5-7). In summary, the general propertes of the common-collector amplfer (emtter follower) nclude an open-loop oltage gan of unty, a large nput resstance and a small output resstance (smlar to the common-dran amplfer). Thus, emtter follower s also used as a buffer or to amplfy the sgnal current (and power) and dre a load. ECE65 Lecture Notes (F. Najmabad), Sprng
10 5.3 Common-Source and Common-Emtter Amplfers Common-Source Confguraton Crcut shown s the generc small-sgnal crcut of a common-dran amplfer (.e., we hae zeroed out all Bas sources). Note that the nput s appled at the gate and the output s taken at the dran. As the source s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common-source amplfer. R G R D If source degeneraton basng s used for the common-source confguraton, a resstor R S should be present. A by-pass capactor s typcally used so that small sgnals by-pass R S, effectely makng the source grounded for small sgnal as s shown. R D R G C R b S We replace the MOS wth ts small-sgnal model. In ths confguraton, R D s parallel to and appears as the load for the transstor. As such, we defne R L R D and the output resstance s taken to the left of R D (see below). Inspecton of the crcut shows that gs. Also, a current of gs flows n r o R L (from the ground to ). Ohm Law: gs (r o R L ) A (r o R L ) A o r o R G G gs _ gs S D r o R D The negate sgn n the gan s ndcate of a 180 phase shft n the output sgnal. Inspectng the crcut, we fnd R / R G (unlateral amplfer). To fnd R o, we set 0. As gs 0, the controlled current source becomes an open crcut and R o r o. If the output resstance s taken to nclude R D (see dscusson n page 5-7), R o R D R o. R G G gs _ gs S D r o R O R L In summary, the general propertes of the common-source amplfer nclude a large open-loop oltage, a large nput resstance (and can be made nfnte wth some basng schemes) but a medum output resstance. ECE65 Lecture Notes (F. Najmabad), Sprng
11 Common-Emtter Confguraton Crcut shown s the generc small-sgnal crcut of a common-emtter amplfer (.e., we hae zeroed out all Bas sources). Note that the nput s appled at the base and the output s taken at the collector. As the emtter s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common-emtter amplfer. R B R C Smlar to the common-dran confguraton, f emtter degeneraton basng s used, a resstor R E should be present wth a by-pass capactor. Ths capactor effectely make the emtter grounded for small sgnal as s shown. R C R B C R b E We now replace the BJT wth ts small sgnal model. In ths confguraton, R C s parallel to and appears as the load for the transstor (R L R C ) and the output resstance s taken to the left of R C n the crcut aboe. C 1 C B C 2 g m π R B r π r R π o C _ E Inspecton of the crcut shows that π. Also, a current of π flows n r o R L (from the ground to ). Ohm Law: π (r o R L) A (r o R L ) r o R L r e A o r o r o r e The negate sgn n the gan s ndcate of a 180 phase shft n the output sgnal. From the crcut, we fnd R / R B r π (a unlateral amplfer) To fnd R o, we set 0. As π 0, the controlled current source becomes an open crcut and R o r o. Smlarly, R o R C R o R C r o. C 1 B C g π m R B r π π r o _ E R L In summary, the general propertes of the common-emtter amplfer nclude a large openloop oltage, a medum nput resstance and a medum to large output resstance. R O ECE65 Lecture Notes (F. Najmabad), Sprng
12 5.4 Common-Source and Common-Emtter Amplfers wth Degeneraton Common-Source Confguraton wth a Source Resstor Crcut shown s the generc small-sgnal crcut of a common-source amplfer wth degeneraton. Note that the nput s appled at the gate and the output s taken at the dran smlar to a common-dran amplfer but a source resstor s now present. R D R G R S We replace the MOS wth ts small-sgnal model. Smlar to the common-dran amplfer, R D s parallel to and appears as the load for the transstor (R L R D and the output resstance s taken to the left of R D n the crcut aboe). Usng nodeoltage method: C 1 C G D 2 gs R G gs r o R D _ S R S Node s : Node : s s gs 0 R S r o R L s r o gs 0 s R S R L 0 where the last equaton s found by summng the frst two. Substtutng for gs s n the frst equaton, computng s, and substtutng n the thrd equaton, we get: A r o ( ) r o R S (1 r o ) r o ( ) r o R S r o A R L 1 R S R L/r o A o r o If r o s large compared to R L and/or f R S and R L of the same order (.e., R L /R S r o ), we can drop the last term to fnd: A 1 R S The amplfer gan s substantally reduced wth the presence of R S but t has become much less senste to change n. Inspectng the crcut we fnd R / R G, smlar to a common-source amplfer. ECE65 Lecture Notes (F. Najmabad), Sprng
13 To fnd R o, we set 0 and compute the Theenn Equalent resstance seen at the output termnals. Because of the presence of the controlled source, we need to attach x oltage source to the crcut and compute x. R G G gs _ gs S D r o R L R G G gs _ gs S D r o x x R S R O R S By KCL, a current of x gs should flow n r o and x should flow n R S. Snce gs R S x : KVL : x r o ( x gs ) R S x r o ( x R S x ) R s x x (r o r o R S R S ) R o x x r o R S r o R S r o (1 R S ) In summary, source degeneraton has led to an amplfer wth a lower gan whch s less senste to transstor parameters and seeral other benefts (e.g., larger band-wdth) whch are beyond the scope of ths course. Common-Emtter Confguraton wth an Emtter Resstor Crcut shown s the generc small-sgnal crcut of a common-emtter amplfer wth degeneraton (.e., wth emtter resstor). Note that the nput s appled at the base and the output s taken at the collector smlar to a common-emtter amplfer. R C R B R E We now replace the BJT wth ts small-sgnal model. Smlar to the common-dran amplfer, R C s parallel to and appears as the load for the transstor (R L R C ) and the output resstance s taken to the left of R C n the crcut aboe. Usng node-oltage method and notng π e : C 1 C B 2 b C g m π RB r π π r o R C _ E R E Node e : Node : 0 e e e π R E r π r o 0 e g m π 0 r o e e 0 R E r π ECE65 Lecture Notes (F. Najmabad), Sprng
14 The thrd equaton s the sum of the frst two. Fndng e from the thrd equaton and substtutng n the 2nd equaton, we get: A R L R E (1 R L /r o)(1 R E /r π ) R L A R E r e ( /r o)(r E r π )/β A o r o r o 1 R E /r π r e R E /β R L R E (1 R L /r o)(r E r π )/β If (R L/r o )/β 1 (a ery good approxmaton), we can drop the last term to fnd: A R L 1 R E R L R E r e whch s the expresson often used. Note that the amplfer gan s reduced wth the presence of R E but t has become substantally less senste to any change n β (only through r e ). From the crcut we fnd R / R B ( / b ). The exact formulaton for / b s cumbersome. A good approxmaton whch leads to a smple expresson s r o R E. In ths case, r o can be remoed from the crcut and b r π ( b π )R E b r π ( b β b )R E b [r π (1 β)r E ] R R B [r π (1 β)r E ] To fnd R o, we set 0 and compute the Theenn Equalent resstance seen at the output termnals. Because of the presence of the controlled source, we need to attach x oltage source to the crcut and compute x. By KCL, current x π wll flow through r o and current x wll flow through R E r π : C 1 B b C π R B r π π _ E R E r o R O R L r π _ π C π E R E r o x x π x (R E r π ) KVL: x ( x π )r o x (R E r π ) x [r o r o (R E r π )] ( R o r o [1 (R E r π )] r o 1 βr ) E r π R E ECE65 Lecture Notes (F. Najmabad), Sprng
15 In summary, emtter degeneraton has led to an amplfer wth a lower gan whch s much less senste to transstor parameters, a substantally larger nput resstance and a somewhat larger output resstance. 5.5 Common-Gate and Common-Base Amplfers Common-Gate Confguraton Crcut shown s the generc small-sgnal crcut of a commongate amplfer. Note that the nput s appled at the source and the output s taken at the dran. As the gate s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common gate amplfer. If the base has to based to a DC alue (for example usng oltage dder crcut shown), a by-pass capactor s added to short the base for small sgnals as s shown wth R G R 2 R 1. R D R S We replacng MOS wth ts small sgnal model. In ths confguraton, R D s parallel to and appears as the load for the transstor. As such, we defne R L R D and the output resstance s taken to the left of R D n the crcut aboe. Notng that gs and wrtng the node equaton at : C b R 1 R2 R D R S R L r o ( ) 0 ( 1 1 ) 1 r o r o r o A (R L r o) r o r o S R S G g m gs _ gs D ro R D A o r o D To fnd R, t s easer to wrte R R S 1 (see crcut). By KCL at node S, current 1 gs wll flow n r o and current 1 wll flow n R L R D. Thus: S 1 R S g m gs _ gs G ro R D ( 1 gs )r o 1 R L 1 r o r o 1 R L ECE65 Lecture Notes (F. Najmabad), Sprng
16 1 r o R L 1 r o 1 R L /r o R R S 1 R L /r o As can be seen, the common-gate amplfer s NOT unlateral.e., R depends on the load. To fnd R o, we set 0. As gs 0, the controlled current source becomes an open crcut and R o r o (Note that R S s shorted out). S RS G g m gs In summary, the general propertes of the common-gate amplfer nclude a large open-loop oltage, a small nput resstance and a medum output resstance (t has the same gan and output resstance alues as that of a common-source confguraton but a much lower nput resstance). _ gs D ro R O R L Common-Base Confguraton Crcut shown s the generc small-sgnal crcut of a commonbase amplfer. Note that the nput s appled at the source and the output s taken at the dran. As the gate s grounded (for small sgnal), t s the common termnal of nput and output. Thus, ths crcut s called the common-gate amplfer. If the base has to based to a DC alue (for example usng oltage dder crcut shown), a by-pass capactor s added to short the base for small sgnals as s shown wth R B R 2 R 1. R C R E We replace the BJT wth ts small sgnal model. In ths confguraton, R C s parallel to and appears as the load for the transstor. As such, we defne R L R C and the output resstance s taken to the left of R C n the crcut aboe. Notng that π and wrtng the node equaton at : C b R 1 R2 R C R E R L r o π 0 ( 1 1 ) 1 r o r o r o A (R L r o ) A o r o r o r o _ r π π B E π R E C r o R C ECE65 Lecture Notes (F. Najmabad), Sprng
17 To fnd R, t s easer to wrte R (R E r π ) 1 (see crcut). By KCL at node E, current 1 π wll flow n r o and current 1 wll flow n R L R C. Thus (settng π ) by KVL: ( 1 π )r o 1 R L 1 r o r o 1 R L 1 r o R L 1 r o 1 R L /r o R R E r π 1 R L /r o As can be seen, the common-base amplfer s NOT unlateral.e., R depends on the load. To fnd R o, we set 0. As π 0, the controlled current source becomes an open crcut and R o r o (Note that R E r π s shorted out). In summary, the common-base confguraton has a large open-loop oltage, a small nput resstance and a medum output resstance (t has the same gan and output resstance alues as that of a common-emtter confguraton but a much lower nput resstance). _ π B E 1 R E E _ π B π r π π R E C r o r π C r o R C R O R L 5.6 Summary of Amplfer Confguratons The common-source (CS) and common-emtter (CE) amplfers hae a hgh gan and are the man confguraton n a practcal amplfer. Ignorng bas resstors R G or R B, the CS confguraton has an nfnte nput resstance whle the CE amplfer has a modest nput resstance. Both CS and CE amplfer hae a rather hgh output resstance r o and a lmted hgh-frequency response (you wll see ths n 102). Addton of source or emtter resstor (degenerated CS or CE) leads to seeral benefts: a gan whch s less senste to temperature, a much larger nput resstance for CE confguraton, a better control of amplfer saturaton, and a much mproed hghfrequency response. Howeer, these are realzed at the expense of a lower gan. The common-gate (CG) and commons-base (CB) amplfers hae a hgh gan (smlar to CS and CE) but a low nput resstance. As such, they are only used for specalzed applcatons. CG and CB amplfers hae an excellent hgh-frequency response. They are typcally used n combnaton wth a CS or CE stage (such as cascode amplfers) The source-follower and emtter-follower confguratons hae a hgh nput resstance, a gan close to unty, and a low output resstance. They are employed as a oltage buffer and/or as the output stage to ncrease the current and power to the load. ECE65 Lecture Notes (F. Najmabad), Sprng
18 5.7 Low Frequency Response of Transstor Amplfers Up to now, we hae neglected the mpact of the couplng and by-pass capactors (assumed they were short crcut). Each of these capactors ntroduce a pole n the response of the crcut. For example, let s consder the couplng capactor at the nput to the amplfer (C c1 n amplfer confguratons that we examned before). We need to perform the analyss n the frequency doman (oltage are represented by captal letter as they are n phasor form): A V o V V V sg V V sg V o V sg R o A o R R R sg 1/(sC c1 ) R R R sg s s ω p1, R R R sg A s s ω p1 2πf p1 ω p1 R sg V sg Cc1 V R 1 C c1 (R R sg ) Ro A V o V o RL Where A s the md-frequency gan that we hae calculated for all transstor confguratons (.e., wth capactors short). As can be seen, the couplng capactor C c1 has ntroduced a low-frequency pole and the amplfer gan falls at low frequences. One may be tempted to compute the mpact of the couplng capactor at the output n a smlar manner. Fgure below s for a common-dran amplfer (wth R D appearng as the load, see fgure n page 5-5). It s straghtforward to show (left as an exercse): V sg R sg V R Ro A V o Cc2 RD V o RL V o V sg R R R sg A s s ω p2 2πf p2 ω p2 1 C c2 ( R D R o ) For unlateral amplfers, f p2 calculated aboe s the pole ntroduced by C c2. Howeer, f the amplfer s NOT unlateral, R depends on the load and the expresson of R wll nclude C c2 as ths capactor s part of the load ( R L R D ( 1/sC c2 )). As such, we need to compute the R /(R R sg ) term to fnd the pole ntroduced by C c2. Ths ssue s specally mportant for amplfers wth small R,.e., common-gate and common-base amplfers. We can stll use the aboe formula, howeer, f we replace R o (output resstance wth 0) wth R out (output resstance wth sg 0). ECE65 Lecture Notes (F. Najmabad), Sprng
19 Smlarly, f a by-pass capactor s present (see page 5-8), t wll ntroduce yet another pole, f p3. The follownethod allows one to compute the poles by nspecton. 1. Zero out V sg. 2. Consder each capactor separately (.e., assume all other capactors are short) 3. Compute, R, the total resstance between the termnals of the capactor. The pole ntroduced by that capactor s gen by f p 1 2πC R Wth all poles assocated wth by-pass and couplng capactors n hand, we can fnd the oerall frequency response of the amplfer as V o V sg A s s ω p1 s s ω p2 s s ω p3 and the lower cut-off frequency s located at 3dB below maxmum alue, A (the mdfrequency gan). If poles are suffcently separated (such as the fgure aboe), the lower cut-off frequency of the amplfer s gen by the hghest-frequency pole. Otherwse, fndng the lower cut-off frequency would be cumbersome. A smple approxmaton for hand calculatons (whch s surprsngly ery good) s to set f l f p1 f p2 f p3 Exercse: Show that the method aboe ges the poles correspondng to C c1 and C C2 (for unlateral amplfer) as was calculated preously. The next two pages nclude a summary of formulas for elementary transstor confguratons. These formulas are correct wthn approxmaton of r o 1 and β 1 both of whch are always ald. Many of these formulas can be smplfed (before pluggng n numbers) as they nclude resstances that are n parallel and typcally one s much smaller (at least a factor of ten) than the others. For example, n a common emtter amplfer, we often fnd that R C and R C r o. Then, r o R C R C and the gan formula can be smplfed to A R C /r e. ECE65 Lecture Notes (F. Najmabad), Sprng
20 Summary of Elementary MOS Confguratons Common Dran (Source Follower): A (R S ) 1 (R S ) R R G R o 1 r o 1 R o R S R o f p2 1/[2πC c2 ( R S R out )] R out 1 R G R S Common Source: A (r o R D ) R R G R o r o R o R D R o R D f p2 1/[2πC c2 ( R D R out )] f pb 1 2πC b [R S (1/ )] R out r o R G R S C b Common Source wth Source Resstance: (R D ) A 1 R S (R D )/r o R R G R D R o r o (1 R S ) R o R D R o R G f p2 1/[2πC c2 ( R D R out )] R out r o (1 R S ) R S Common Gate: A (r o R D ) R R S [1/ (R D )/ r o ] R 1 C b R D R o r o R o R D R o f p2 1/[2πC c2 ( R D R out )] R out r o (1 R S ) R S f pb 1/[2πC b R G ] f l Σ j f pj and f p1 1/[2πC c1 (R R sg )]. ECE65 Lecture Notes (F. Najmabad), Sprng
21 Summary of Elementary BJT Confguratons Common Collector (Emtter Follower): A (R E ) 1 (R E ) R E R E r e R R B [r π (1 β)(r o R E )] R o r π 1 1 r e f p2 1/[2πC c2 ( R E R out )] Common Emtter: R o R E R o A (r o R C ) r o R C r e R R B r π R o r o R o R C R o f p2 1/[2πC c2 ( R C R out )] f pb 1 2πC b [R E (r e (R B R sg )/β)] R B ( ) rπ R B R sg R out r o r e 1 β R out r o R E R B R C R E C b Common Emtter wth Emtter Resstor: A (R C ) R C 1 g m R E R E r e R R R B [r π (1 β)r E ] B ( R o r o [1 (R E r π )] r o 1 βr ) E R o r π R R C R o E ) βr E f p2 1/[2πC c2 ( R C R out )] R out r o (1 r π R E R B R sg Common Base: R C R E A (r o R C ) r o R C r e R R E r π [1/ (R C )/( r o )] R B C b R C R o r o R o R C R o ) βr E f p2 1/[2πC c2 ( R C R out )] R out r o (1 r π R E R B R sg RE f pb 1/[2πC b R CB ] R CB R B [r π (1 β)(r sg R E )] ECE65 Lecture Notes (F. Najmabad), Sprng
22 5.8 Exercse Problems Problem 1 to 3: Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Problem 4: If V cos(ωt) n the crcut of Problem 3, what s the maxmum alue of V for ths crcut to work properly? Problem 5 to 14: Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. 9 V 9 V 9 V 18k 0.47 µ F 18k 0.47 µ F 0.47 F 4 V µ 0.47 µ F o 22k 0.47 µ F 0.47 µ F 22k 22k 18k 5 V Problem 1 Problem 2 Problem 3 Problem 5 15 V 15 V 4 V 4 V 34k 100 nf 5.9k µ F 0.47 µ F o o 4.7 µ F 4.7 µ F 100 nf 4.3mA 4.3mA 5.9k µ F 34k V EE V EE Problem 6 Problem 7 Problem 8 Problem 9 15 V 15 V 34k 100 nf 3V V EE 34k 100 nf 4.7 µ F 2.3k 47 µ F 1mA 47 µ F 4.7 µ F 5.9k k µ F 2.3k 3V 100 nf 2.3k 3V 100 nf Problem 10 Problem 11 Problem 12 Problem 13 ECE65 Lecture Notes (F. Najmabad), Sprng
23 Problem Fnd the bas pont and amplfer parameters of ths crcut (V tn 4 V, V tp 4 V, k (W/L) 0.4 ma/v 2, Ignore the channel-wdth modulaton effect n basng calculatons. Fnd the saturaton oltages for ths amplfer. Problem Fnd the bas pont and amplfer parameters of ths crcut (V tn 1 V, V tp 1 V, k p (W/L) k n (W/L) 0.8 ma/v2, λ 0.01 V 1 ). Ignore the channel-wdth modulaton effect n basng calculatons. Fnd the saturaton oltages for ths amplfer. 2.5 V 18 V 10nF 1 µ F 13k 1.3M 0.47 µ F 0.47 µ F 13V 0.47 µ F o V SS 0.71 ma 0.47 µ F k 500k 5V 5V Problem 14 Problem 15 Problem 16 Problem V 15 V 15V 5 V 0.71 ma 0.47 µ F 1.8M 1.2M 1 µ F 1.8M 1.2M 1 µ F 1.2M 1.8M 1 µ F V SS Problem 18 Problem 19 Problem 20 Problem 21 9V 6V 1 µ F 15V 1.2M 1.8M o Problem 22 Problem 23 Problem 24 Problem M 1.2M 15 V 1 µ F 6V 9V ECE65 Lecture Notes (F. Najmabad), Sprng
24 Problems 27 to 29: Fnd the bas pont of each BJT, the oerall gan ( / ), and the lower cut-off frequency of ths amplfer parameters (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). 2.5 V 15 V 15 V 1M 10nF 33k 4.7 µ F 2k Q1 18k 0.47 µ F Q2 33k 4.7 µ F 2k Q1 Q2 o 1M 6.2k k 6.2k 500 Problem 26 Problem 27 Problem V 15k 3.6k 1.5k 4.7 µ F 2.7k Q1 510 Q2 510 Problem 29 ECE65 Lecture Notes (F. Najmabad), Sprng
25 5.9 Soluton to Selected Exercse Problems Problem 1. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Bas: 9 V Set 0 and capactors open. Replace R 1 and R 2 wth ther Theenn equalent: 18k R B 18 k 22 k 9.9 kω V BB V 0.47 µ F 22k KVL: V BB R B I B V BE 10 3 I E I B I E 1 β I E 201 ( ) I E V BB R B 9 V I E 4 ma I C, I B I C β 20 µa KVL: 9 V CE 10 3 I E V CE V Bas summary: I E I C 4 ma, I B 20 µa, V CE 5 V Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 2.60 k r e 1 13 Ω r o V A V CE k I C µ F o 9.9k Note that we could hae gnored V CE compared to V A n the aboe expresson for r o. Proceedng wth the small sgnal analyss, we zero bas sources (see crcut). As the nput s at the base and output s at the emtter, ths s a common-collector amplfer (emtter follower). Usng formulas of page 5-21 and notng, R E r o, and R E r e : A R E R E r e R E R E r e 1 R R B [r π (1 β)r E ] (9.9 k) (203.6 k) 9.9 k R B R o r e 13 Ω 1 f l f p1 2πC c1 (R R sg ) 1 34 Hz 2π ECE65 Lecture Notes (F. Najmabad), Sprng
26 Problem 2. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Ths s the same crcut as Problem 1 wth excepton of C c2 and. The bas pont s exactly the same. As R E, the amplfer parameters are the same except f l f p1 f p2 37 Hz. Problem 3. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Ths crcut s smlar to Problem 1 expect that the transstor s based wth two oltage sources (alues are chosen to ge the same bas pont). Bas: Set 0 and capactors open: 4 V 5 V 0.47 µ F o BE-KVL: 0 V BE 10 3 I E 5 4 V I E 4.3mA I C, I B I C β 21.5 µa CE-KVL: 4 V CE 10 3 I E 5 V CE V Bas summary: I E I C 4.3 ma, I B 21.5 µa, V CE 4.7 V 5 V Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 2.42 k r e Ω r o V A V CE k I C µ F o Proceedng wth the small sgnal analyss, we zero bas sources (see crcut). As the nput s at the base and output s at the emtter, ths s a common-collector amplfer (emtter follower). Usng formulas of page 5-21 and notng R E, R E r o, and R E r e : A R E R E r e R E R E r e 1 R R B [r π (1 β)r E ] r π (1 β)r E k R o r e 12 Ω 1 f l f p2 2πC c2 ( R E r e ) 1 2πC c2 ( r e ) Hz 2πC c2 ECE65 Lecture Notes (F. Najmabad), Sprng
27 Problem 4: If V cos(ωt) n the crcut of Problem 3, what s the maxmum alue of V for ths crcut to work properly? For the amplfer to work properly, the BJT has to reman n the acte state,.e, E I E e > 0 and CE V CE ce > V D0 0.7 V. The frst equaton ges a mnmum alue for e (or C > 0 ges a mnmum alue for c ). Combnaton of the 2nd equaton and CE-KVL ges a maxmum alue for e (or c ). Lmts on can be found from the two lmts for e (e.g., n ths problem 10 3 e as R E ). /A then ges the range for : E I E e > 0 e > I E 4.3 ma 10 3 e > 4.3 V CE-KVL 4 CE 10 3 E E < 9 CE CE > V D E 10 3 (I E e ) < 8.3 V 10 3 e < 4.0 V 4.3 < A < 4.0 V 4.3 < < 4.0 V V < 4.0 V Problem 5. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly). Ths s the PNP analog of crcut of Problem 2. Bas summary: I E I C 4 ma, I B 20 µa, V EC 5 V Small-Sgnal: /Ω, r e 13 Ω, r π 2.60k, and r o 38.8 k. Amp response: A 1, R 9.9 k, R o 13 Ω, and f l f p1 f p2 37 Hz. Max sgnal: 4.3 < A < < < 4.0 V < 4.0 V Problem 6. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Ths crcut s smlar to the crcut of Problem 3 except that the transstor s based wth a current source. Bas: Set 0 and capactors open. I E 4.3 ma I C, I B I C β BE-KVL: 0 V BE V E V E 0.7 V CE-KVL: 4 V CE V E V CE 4.7 V 21.5 µa 4 V 4.3mA V EE 4 V 0.47 µ F o Bas summary: I E I C 4.3 ma, I B 21.5 µa, V CE 4.7 V V E 4.3mA V EE ECE65 Lecture Notes (F. Najmabad), Sprng
28 Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 2.42 k r e Ω r o V A V CE k I C µ F o Amplfer Response: we zero bas sources (the current source becomes an open crcut. As the nput s at the base and output s at the emtter, ths s a common-collector amplfer (emtter follower) wth R E. Usng formulas of page 5-21 and notng R E r e A R E R E r e r e 1 R R B [r π (1 β)r E ] f l f p2 R o r e 12 Ω 1 2πC c2 ( R E r e ) 1 2πC c2 ( r e ) Hz 2πC c2 BJT s n acte f C E > 0 and CE > V D0. The current source makes the problem slghtly complcated ( e flows through the 100 k resstor whle I E s fed by the current source). As such, CE-KVL degenerates nto two equatons, one for small sgnal and one for basng: CE-KVL (SS) 0 ce 10 5 e and CE V CE ce > V D0 0.7 ce 10 5 e > 0.7 V CE 4.0 V 10 5 e < 4.0 V E I E e > 0 e > I E 4.3 ma 10 5 e > 430 V 430 < A < 4.0 V 430 < < 4 V V < 4.0 V Note that the aboe lmt s correct ONLY for an deal current source (that s why the lower lmt for s so large). In practcal applcatons, the current source wll mpose a condton on E (e.g., mnmum oltage on the collector of a current mrror). Problem 7. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Ths crcut s smlar to the crcut of Problem 6 except that C c2 s remoed. Bas: Set 0 and capactors open. BE-KVL: 0 V BE V E V E 0.7 V 4 V 4.3mA V EE o 4 V 4.3mA V EE V E 1 ECE65 Lecture Notes (F. Najmabad), Sprng
29 KCL 1 V E 7 µa I E ma I E 3 ma I C, I B I C β CE-KVL: 4 V CE V E V CE 4.7 V 15 µa Bas summary: I E I C 4.3 ma, I B 21.5 µa, V CE 4.7 V whch s the exactly the same as of that of Problem 6. The small-sgnal, amplfer parameters, and maxmum and are exactly the same as those of Problem 6 expect f l 0 (.e., ths amplfer can amplfy DC sgnals). Problem 8. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Bas: 15 V Set 0 and capactors open. Replace R 1 and R 2 wth ther Theenn equalent: 34k 100 nf R B 5.9 k 34 k 5.0 k, V BB V 4.7 µ F 5.9k µ F BE-KVL: V BB R B I B V BE 510I E I B I E 1 β I E 201 ( ) I E k 15 V CE-KVL: I E 3 ma I C, I B I C β V CC 1000I C V CE 510I E 15 µa V CE 15 1, V Bas summary: I E I C 3 ma, I B 15 µa, V CE 10.5 V Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 3.47 k r e Ω r o V A V CE I C k 5.9k V 4.95V 5.0k 510 ECE65 Lecture Notes (F. Najmabad), Sprng
30 Proceedng wth the small sgnal analyss, we zero bas sources (see crcut). As the nput s at the base and output s at the collector, ths s a common-emtter amplfer (wth NO emtter resstor). Usng formulas of page 5-21 and notng R C, R C r o, R E r e, and R sg 0: 4.7 µ F 5.0k 510 A r o R C r e R C r e 58 R R B r π k R out R o r o 53.5 k 1 f p1 2πC c1 (R R sg ) Hz 2π f p2 f pb 1 2πC c2 ( R C R out ) 1 2πC c2 ( R c ) 1 2πC c Hz 1 2πC b [R E (r e (R B R sg )/β)] Hz 2πC b [R E 17.3] f l f p1 f p2 f pb Hz To fnd the maxmum ampltude for, we note that c R C 10 3 c (as R C ): CE-KVL (I C C ) CE 510I E As e does not flow n the R E 510 Ω resstor because of the 47 µf by-pass capactor, CE-KVL CE 15 1, 510I C 10 3 c c CE > V D0 0.7 c < 9.8 ma 10 3 c < 9.8 V C I C c > 0 c > I C 3 ma 10 3 c > 3 V 3 < 58 < 9.8 V 0.17 < < V Problem 9. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Ths s the PNP analog of crcut of Problem 8. Bas summary: I E I C 3 ma, I B 15 µa, V EC 10.5 V Small-Sgnal: /Ω, r e 17.3 Ω. r π 3.47k, and r o 53.5 k. Amp response: A 58, R 2.05 k, R o 53.5 k, and f l f p1 f p2 f pb 113 Hz. ECE65 Lecture Notes (F. Najmabad), Sprng
31 Problem 10. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Bas: 15 V Set 0 and capactors open. The bas crcut s exactly that of Problem 8 wth R B 5.0 k. Bas summary: I E I C 3 ma, I B 15 µa, V CE 10.5 V. Small-Sgnal: The small-sgnal parameters are also the same as those of Problem 8: /Ω, r e 17.3 Ω. r π 3.47k, and r o 53.5 k. Proceedng wth the small sgnal analyss, we zero bas sources (see crcut). As the nput s at the base and output s at the collector, ths s a degenerated common-emtter amplfer (.e, wth a emtter resstor). Usng formulas of page 5-21 and notng R C, R C r o, and R E r e : 34k 4.7 µ F 5.9k k 100 nf 15 V A R C R C 1.90 R E r e R E r e R R B [r π (1 β)r E ] R B [(1 β)r E ] R B 5.0 k R o r o [1 (R E r π )] r o [ (510 3, 470)] M ) βr E R out r o (1 26.6r o 1.4 M r π R E R B R sg f p1 f p2 1 2πC c1 (R R sg ) Hz 2π µ F 1 2πC c2 ( R C R out ) 1 2πC c2 ( R c ) 1 2πC c Hz f l f p1 f p Hz 5.0k 5.9k To fnd the maxmum ampltude for, we need to fnd c as c R C 10 3 c (as R C ). Then, (note compared to Problem 8, e now flows n the R E 510 Ω resstor:) CE-KVL (I C C ) CE 510(I E e ) CE 15 1, 510I C 1, 510 c , 510 c CE > V D0 0.7 c < 6.5 ma 10 3 c < 6.5 V C I C c > 0 c > I C 3 ma 10 3 c > 3 V 3 < 1.9 < 6.5 V 3.42 < < 1.58 V ECE65 Lecture Notes (F. Najmabad), Sprng
32 Problem 11. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Bas: Set 0 and capactors open. Because the 47 µf capactor across the 240 Ω resstor becomes an open crcut, the total R E for bas s Ω and the bas crcut s exactly that of Problem 8 wth R B 5.0 k. Bas summary: I E I C 3 ma, I B 15 µa, V CE 10.5 V. Small-Sgnal: The small-sgnal parameters are also the same as those of Problem 8: /Ω, r e 17.3 Ω. r π 3.47k, and r o 53.5 k. 34k 4.7 µ F 5.9k 15 V nf 47 µ F 15 V Proceedng wth the small sgnal analyss, we zero bas sources (see crcut). In ths case, the 47 µf capactor across the 240 Ω resstor becomes a short crcut and the total R E for small-sgnal s 270 Ω. As the nput s at the base and output s at the collector, ths s a degenerated commonemtter amplfer (.e, wth a emtter resstor). Usng formulas of page 5-21 and notng R C, R C r o, and R E r e : 34k 5.9k A R C R C 3.48 R E r e R E r e R R B [r π (1 β)r E ] R B [(1 β)r E ] R B 5.0 k R o r o [1 (R E r π )] r o [ (270 3, 470)] k ) βr E R out r o (1 15.4r o 826 k r π R E R B R sg f p1 f p2 1 2πC c1 (R R sg ) Hz 2π k 4.7 µ F 1 2πC c2 ( R C R out ) 1 2πC c2 ( R c ) Hz 2πC c2 5.9k 15 V 100 nf We need to fnd the pole ntroduced by the 47 µf by-pass capactor, f pb. Although ths confguraton was not ncluded n the formulas for BJT elementary confguraton of page 5-21, we can extend those formulas to coer ths case. ECE65 Lecture Notes (F. Najmabad), Sprng
33 The pole ntroduced by the by-pass capactor n the common emtter case s (see fgure) f pb 1 2πC b [R E (r e (R B R sg )/β)] R C Per our dscusson of page 5-19 on how to fnd poles ntroduced by each capactor, R E (r e (R B R sg )/β)] s the total resstance seen across the termnal of C b. As can be seen from the crcut, the resstance across C b termnals conssts of two resstors n parallel, R E and R e, the resstance seen through the emtter of the BJT: R e r e (R B R sg )/β) from the formula aboe. For the crcut here (defned R E1 240 Ω and R E2 270 Ω), the resstance across C b s made of two resstances n parallel: R E1 and the combnaton of R E2 and R e, the resstance seen through the emtter of BJT n seres. Thus: f pb f pb 1 2πC b [R E1 (R E2 r e (R B R sg )/β)] 1 2πC b [240 (270 17] Hz 2π f l f p1 f p Hz R B 34k 4.7 µ F 5.9k R e R E R E2 R E1 15 V R e C b 100 nf 47 µ F To fnd the maxmum ampltude for, we need to fnd c as c R C 10 3 c (as R C ). Then, (note e now flows n 270 Ω resstor whle I E flows n a 510 Ω resstor): CE-KVL (I C C ) CE 510I E 270 e CE 15 1, 510I C 1, 270 c , 270 c CE > V D0 0.7 c < 7.7 ma 10 3 c < 7.7 V C I C c > 0 c > I C 3 ma 10 3 c > 3 V 3 < 3.5 < 7.7 V 2.2 < < 0.86 V ECE65 Lecture Notes (F. Najmabad), Sprng
34 Problem 12. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Bas: Set 0 and capactors open. BE-KVL: 3 2.3I E V EB I E 1 ma I C, I B I E 1 β 5 µa CE-KVL: I E V EC I C 3 V EC V Bas summary: I E I C 1 ma, I B 50 µa, V CE 1.4 V 3V 2.3k 2.3k 3V 3V 2.3k 100 nf 47 µ F Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 10.4 k r e 1 52 Ω r o V A V CE I C k k 3V Proceedng wth the small sgnal analyss, we zero bas sources. As the nput s at the base and output s at the collector, ths s a common-emtter amplfer. It does not hae an emtter resstor as 47 µf capactor shorts out R E for small sgnals. Usng formulas of page 5-21 and notng R C, R C r o, and R E r e : A r o R C R C 44.2 r e r e R R B r π 10.4 k R out R o r o 151 k f p1 0 f p2 f pb 1 2πC c2 ( R C R out ) 1 2πC c2 ( R c ) 15.9 Hz 1 2πC b [R E (r e (R B R sg )/β)] 1 2πC b [R E 52] 66.6Hz f l f p1 f p2 f pb Hz ECE65 Lecture Notes (F. Najmabad), Sprng
35 To fnd the maxmum ampltude for, we need to fnd c as c R C c (as R C ). Then, (note only I E flows n R E 2.3 k resstor): CE-KVL (I C C ) CE I E 3 CE I C c c CE > V D0 0.7 c < 0.3 ma c < 0.7 V C I C c > 0 c > I C 1 ma c > 2.3 V 2.3 < 44.2 < 0.7 V < < V Problem 13. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Ths s the same crcut as that of Problem 13 expect that the transstor s based wth a current source Bas: Set 0 and capactors open. From the crcut I E 1 ma BE-KVL: I E 1 ma I C, V E V EB 0.7 V I B I C β 5 µa CE-KVL: V E V CE I C 3 V CE 0.7 V CE 1.4 V V EE 1mA 2.3k 3V V EE 1mA V E 100 nf 47 µ F Bas summary: I E I C 1 ma, I B 50 µa, V CE 1.4 V. Small-Sgnal: As the bas pont s exactly the same as that of problem 12, we hae: /Ω, r e 52 Ω, r π 10.4k, and r o 151 k. Amplfer response: The only dfference wth problem 12 s that R E n ths crcut: A 44.2, R 10.4 k, R o 151 k, and f l Hz. Maxmum ampltude for : note only I E flows n the current source whle e flows through the by-pass capactor. As such, the results are smlar to those of problem 12: 2.3 < 44.2 < 0.7 V or < < V. 2.3k 3V ECE65 Lecture Notes (F. Najmabad), Sprng
36 Problem 14. Fnd the bas pont and amplfer parameters of ths crcut (S BJT wth n 2, β 200 and V A 150 V. Ignore the Early effect n basng calculatons). Fnd the maxmum ampltude of for the crcut to work properly. Bas: Set 0 and capactors open. 2.5 V R B 12 k 13 k 6.24 k, V BB V BE-KVL: V BB R B I B V BE 510I E I B I E 1 β I E 201 ( ) I E nF 1 µ F V 13k 13k 12k CE-KVL: I E 1.16 ma I C, I C V CE 400I E I B I C β 5.8 µa k V CE 2.5 1, V Bas summary: I E I C 1.16 ma, I B 5.8 µa, V CE 0.88 V Small-Sgnal: Frst we calculate the small-sgnal parameters: I C nv T r π β 8.97 k r e Ω r o V A V CE I C k Proceedng wth the small sgnal analyss, we zero bas sources. As the nput s at the emtter and output s at the collector, ths s a common-base amplfer. Usng formulas of page 5-21 and notng, and R C r o : A (r o R C ) R C 22.3 R R E r π [1/ (R C )/( r o )] R E r π (1/ ) R 400 8, Ω ) βr E R out r o (1 r π R E R B R sg R out r o [ /(8, )] 9.54r o 1.2 M f p1 1/[2πC c1 (R R sg )] 3.95 khz R o r o 129 k ECE65 Lecture Notes (F. Najmabad), Sprng
37 f p2 1 2πC c2 ( R C R out ) 0 R CB R B [r π (1 β)(r sg R E )] 6.24 k 8.97 k 3.68 k 1 f pb 432 Hz 2πC b R CB f l f p1 f p2 f pb 3, khz Note the small nput resstance of ths amplfer and correspondng large f p1. To fnd the maxmum ampltude for, we need to fnd c as c R C 10 3 c (as R C ): CE-KVL (I C C ) CE 400(I E e ) CE 2.5 1, 400I C 1, 400 c , 400 c CE > V D0 0.7 c < 0.13 ma 10 3 c < 0.18 V C I C c > 0 c > I C 1.16 ma 10 3 c > 1.16 V 1.16 < 22.3 < 0.18 V 52 < < 8 mv ECE65 Lecture Notes (F. Najmabad), Sprng
+ + + - - This circuit than can be reduced to a planar circuit
MeshCurrent Method The meshcurrent s analog of the nodeoltage method. We sole for a new set of arables, mesh currents, that automatcally satsfy KCLs. As such, meshcurrent method reduces crcut soluton to
More informationLinear Circuits Analysis. Superposition, Thevenin /Norton Equivalent circuits
Lnear Crcuts Analyss. Superposton, Theenn /Norton Equalent crcuts So far we hae explored tmendependent (resste) elements that are also lnear. A tmendependent elements s one for whch we can plot an / cure.
More informationThe circuit shown on Figure 1 is called the common emitter amplifier circuit. The important subsystems of this circuit are:
polar Juncton Transstor rcuts Voltage and Power Amplfer rcuts ommon mtter Amplfer The crcut shown on Fgure 1 s called the common emtter amplfer crcut. The mportant subsystems of ths crcut are: 1. The basng
More information(6)(2) (-6)(-4) (-4)(6) + (-2)(-3) + (4)(3) + (2)(-3) = -12-24 + 24 + 6 + 12 6 = 0
Chapter 3 Homework Soluton P3.-, 4, 6, 0, 3, 7, P3.3-, 4, 6, P3.4-, 3, 6, 9, P3.5- P3.6-, 4, 9, 4,, 3, 40 ---------------------------------------------------- P 3.- Determne the alues of, 4,, 3, and 6
More informationMultiple stage amplifiers
Multple stage amplfers Ams: Examne a few common 2-transstor amplfers: -- Dfferental amplfers -- Cascode amplfers -- Darlngton pars -- current mrrors Introduce formal methods for exactly analysng multple
More informationThe Full-Wave Rectifier
9/3/2005 The Full Wae ectfer.doc /0 The Full-Wae ectfer Consder the followng juncton dode crcut: s (t) Power Lne s (t) 2 Note that we are usng a transformer n ths crcut. The job of ths transformer s to
More informationChapter 6 Inductance, Capacitance, and Mutual Inductance
Chapter 6 Inductance Capactance and Mutual Inductance 6. The nductor 6. The capactor 6.3 Seres-parallel combnatons of nductance and capactance 6.4 Mutual nductance 6.5 Closer look at mutual nductance Oerew
More informationFaraday's Law of Induction
Introducton Faraday's Law o Inducton In ths lab, you wll study Faraday's Law o nducton usng a wand wth col whch swngs through a magnetc eld. You wll also examne converson o mechanc energy nto electrc energy
More informationPeak Inverse Voltage
9/13/2005 Peak Inerse Voltage.doc 1/6 Peak Inerse Voltage Q: I m so confused! The brdge rectfer and the fullwae rectfer both prode full-wae rectfcaton. Yet, the brdge rectfer use 4 juncton dodes, whereas
More informationSection C2: BJT Structure and Operational Modes
Secton 2: JT Structure and Operatonal Modes Recall that the semconductor dode s smply a pn juncton. Dependng on how the juncton s based, current may easly flow between the dode termnals (forward bas, v
More information8.5 UNITARY AND HERMITIAN MATRICES. The conjugate transpose of a complex matrix A, denoted by A*, is given by
6 CHAPTER 8 COMPLEX VECTOR SPACES 5. Fnd the kernel of the lnear transformaton gven n Exercse 5. In Exercses 55 and 56, fnd the mage of v, for the ndcated composton, where and are gven by the followng
More informationThe OC Curve of Attribute Acceptance Plans
The OC Curve of Attrbute Acceptance Plans The Operatng Characterstc (OC) curve descrbes the probablty of acceptng a lot as a functon of the lot s qualty. Fgure 1 shows a typcal OC Curve. 10 8 6 4 1 3 4
More informationImplementation of Deutsch's Algorithm Using Mathcad
Implementaton of Deutsch's Algorthm Usng Mathcad Frank Roux The followng s a Mathcad mplementaton of Davd Deutsch's quantum computer prototype as presented on pages - n "Machnes, Logc and Quantum Physcs"
More informationSmall-Signal Analysis of BJT Differential Pairs
5/11/011 Dfferental Moe Sall Sgnal Analyss of BJT Dff Par 1/1 SallSgnal Analyss of BJT Dfferental Pars Now lets conser the case where each nput of the fferental par conssts of an entcal D bas ter B, an
More informationbenefit is 2, paid if the policyholder dies within the year, and probability of death within the year is ).
REVIEW OF RISK MANAGEMENT CONCEPTS LOSS DISTRIBUTIONS AND INSURANCE Loss and nsurance: When someone s subject to the rsk of ncurrng a fnancal loss, the loss s generally modeled usng a random varable or
More informationCalculation of Sampling Weights
Perre Foy Statstcs Canada 4 Calculaton of Samplng Weghts 4.1 OVERVIEW The basc sample desgn used n TIMSS Populatons 1 and 2 was a two-stage stratfed cluster desgn. 1 The frst stage conssted of a sample
More informationOptical Signal-to-Noise Ratio and the Q-Factor in Fiber-Optic Communication Systems
Applcaton ote: FA-9.0. Re.; 04/08 Optcal Sgnal-to-ose Rato and the Q-Factor n Fber-Optc Communcaton Systems Functonal Dagrams Pn Confguratons appear at end of data sheet. Functonal Dagrams contnued at
More informationBERNSTEIN POLYNOMIALS
On-Lne Geometrc Modelng Notes BERNSTEIN POLYNOMIALS Kenneth I. Joy Vsualzaton and Graphcs Research Group Department of Computer Scence Unversty of Calforna, Davs Overvew Polynomals are ncredbly useful
More informationChapter 31B - Transient Currents and Inductance
Chapter 31B - Transent Currents and Inductance A PowerPont Presentaton by Paul E. Tppens, Professor of Physcs Southern Polytechnc State Unversty 007 Objectves: After completng ths module, you should be
More information1 Example 1: Axis-aligned rectangles
COS 511: Theoretcal Machne Learnng Lecturer: Rob Schapre Lecture # 6 Scrbe: Aaron Schld February 21, 2013 Last class, we dscussed an analogue for Occam s Razor for nfnte hypothess spaces that, n conjuncton
More informationRecurrence. 1 Definitions and main statements
Recurrence 1 Defntons and man statements Let X n, n = 0, 1, 2,... be a MC wth the state space S = (1, 2,...), transton probabltes p j = P {X n+1 = j X n = }, and the transton matrx P = (p j ),j S def.
More informationCalculating the high frequency transmission line parameters of power cables
< ' Calculatng the hgh frequency transmsson lne parameters of power cables Authors: Dr. John Dcknson, Laboratory Servces Manager, N 0 RW E B Communcatons Mr. Peter J. Ncholson, Project Assgnment Manager,
More informationv a 1 b 1 i, a 2 b 2 i,..., a n b n i.
SECTION 8.4 COMPLEX VECTOR SPACES AND INNER PRODUCTS 455 8.4 COMPLEX VECTOR SPACES AND INNER PRODUCTS All the vector spaces we have studed thus far n the text are real vector spaces snce the scalars are
More informationInstitute of Informatics, Faculty of Business and Management, Brno University of Technology,Czech Republic
Lagrange Multplers as Quanttatve Indcators n Economcs Ivan Mezník Insttute of Informatcs, Faculty of Busness and Management, Brno Unversty of TechnologCzech Republc Abstract The quanttatve role of Lagrange
More information"Research Note" APPLICATION OF CHARGE SIMULATION METHOD TO ELECTRIC FIELD CALCULATION IN THE POWER CABLES *
Iranan Journal of Scence & Technology, Transacton B, Engneerng, ol. 30, No. B6, 789-794 rnted n The Islamc Republc of Iran, 006 Shraz Unversty "Research Note" ALICATION OF CHARGE SIMULATION METHOD TO ELECTRIC
More informationSPEE Recommended Evaluation Practice #6 Definition of Decline Curve Parameters Background:
SPEE Recommended Evaluaton Practce #6 efnton of eclne Curve Parameters Background: The producton hstores of ol and gas wells can be analyzed to estmate reserves and future ol and gas producton rates and
More informationWhat is Candidate Sampling
What s Canddate Samplng Say we have a multclass or mult label problem where each tranng example ( x, T ) conssts of a context x a small (mult)set of target classes T out of a large unverse L of possble
More information8 Algorithm for Binary Searching in Trees
8 Algorthm for Bnary Searchng n Trees In ths secton we present our algorthm for bnary searchng n trees. A crucal observaton employed by the algorthm s that ths problem can be effcently solved when the
More informationModule 2 LOSSLESS IMAGE COMPRESSION SYSTEMS. Version 2 ECE IIT, Kharagpur
Module LOSSLESS IMAGE COMPRESSION SYSTEMS Lesson 3 Lossless Compresson: Huffman Codng Instructonal Objectves At the end of ths lesson, the students should be able to:. Defne and measure source entropy..
More informationSection 5.4 Annuities, Present Value, and Amortization
Secton 5.4 Annutes, Present Value, and Amortzaton Present Value In Secton 5.2, we saw that the present value of A dollars at nterest rate per perod for n perods s the amount that must be deposted today
More informationRESEARCH ON DUAL-SHAKER SINE VIBRATION CONTROL. Yaoqi FENG 1, Hanping QIU 1. China Academy of Space Technology (CAST) yaoqi.feng@yahoo.
ICSV4 Carns Australa 9- July, 007 RESEARCH ON DUAL-SHAKER SINE VIBRATION CONTROL Yaoq FENG, Hanpng QIU Dynamc Test Laboratory, BISEE Chna Academy of Space Technology (CAST) yaoq.feng@yahoo.com Abstract
More informationNOTE: The Flatpak version has the same pinouts (Connection Diagram) as the Dual In-Line Package. *MR for LS160A and LS161A *SR for LS162A and LS163A
BCD DECADE COUNTERS/ 4-BIT BINARY COUNTERS The LS160A/ 161A/ 162A/ 163A are hgh-speed 4-bt synchronous counters. They are edge-trggered, synchronously presettable, and cascadable MSI buldng blocks for
More informationTexas Instruments 30X IIS Calculator
Texas Instruments 30X IIS Calculator Keystrokes for the TI-30X IIS are shown for a few topcs n whch keystrokes are unque. Start by readng the Quk Start secton. Then, before begnnng a specfc unt of the
More informationChapter 12 Inductors and AC Circuits
hapter Inductors and A rcuts awrence B. ees 6. You may make a sngle copy of ths document for personal use wthout wrtten permsson. Hstory oncepts from prevous physcs and math courses that you wll need for
More informationQuantization Effects in Digital Filters
Quantzaton Effects n Dgtal Flters Dstrbuton of Truncaton Errors In two's complement representaton an exact number would have nfntely many bts (n general). When we lmt the number of bts to some fnte value
More informationVRT012 User s guide V0.1. Address: Žirmūnų g. 27, Vilnius LT-09105, Phone: (370-5) 2127472, Fax: (370-5) 276 1380, Email: info@teltonika.
VRT012 User s gude V0.1 Thank you for purchasng our product. We hope ths user-frendly devce wll be helpful n realsng your deas and brngng comfort to your lfe. Please take few mnutes to read ths manual
More informationHow Sets of Coherent Probabilities May Serve as Models for Degrees of Incoherence
1 st Internatonal Symposum on Imprecse Probabltes and Ther Applcatons, Ghent, Belgum, 29 June 2 July 1999 How Sets of Coherent Probabltes May Serve as Models for Degrees of Incoherence Mar J. Schervsh
More informationTHE METHOD OF LEAST SQUARES THE METHOD OF LEAST SQUARES
The goal: to measure (determne) an unknown quantty x (the value of a RV X) Realsaton: n results: y 1, y 2,..., y j,..., y n, (the measured values of Y 1, Y 2,..., Y j,..., Y n ) every result s encumbered
More informationLaddered Multilevel DC/AC Inverters used in Solar Panel Energy Systems
Proceedngs of the nd Internatonal Conference on Computer Scence and Electroncs Engneerng (ICCSEE 03) Laddered Multlevel DC/AC Inverters used n Solar Panel Energy Systems Fang Ln Luo, Senor Member IEEE
More informationLecture 3: Force of Interest, Real Interest Rate, Annuity
Lecture 3: Force of Interest, Real Interest Rate, Annuty Goals: Study contnuous compoundng and force of nterest Dscuss real nterest rate Learn annuty-mmedate, and ts present value Study annuty-due, and
More informationAn Alternative Way to Measure Private Equity Performance
An Alternatve Way to Measure Prvate Equty Performance Peter Todd Parlux Investment Technology LLC Summary Internal Rate of Return (IRR) s probably the most common way to measure the performance of prvate
More informationRing structure of splines on triangulations
www.oeaw.ac.at Rng structure of splnes on trangulatons N. Vllamzar RICAM-Report 2014-48 www.rcam.oeaw.ac.at RING STRUCTURE OF SPLINES ON TRIANGULATIONS NELLY VILLAMIZAR Introducton For a trangulated regon
More informationSupport Vector Machines
Support Vector Machnes Max Wellng Department of Computer Scence Unversty of Toronto 10 Kng s College Road Toronto, M5S 3G5 Canada wellng@cs.toronto.edu Abstract Ths s a note to explan support vector machnes.
More informationLuby s Alg. for Maximal Independent Sets using Pairwise Independence
Lecture Notes for Randomzed Algorthms Luby s Alg. for Maxmal Independent Sets usng Parwse Independence Last Updated by Erc Vgoda on February, 006 8. Maxmal Independent Sets For a graph G = (V, E), an ndependent
More informationThe Bridge Rectifier
9/4/004 The Brdge ectfer.doc 1/9 The Brdge ectfer Now consder ths juncton dode rectfer crcut: 1 Lne (t) - O (t) _ 4 3 We call ths crcut the brdge rectfer. Let s analyze t and see what t does! Frst, we
More informationHow To Calculate The Accountng Perod Of Nequalty
Inequalty and The Accountng Perod Quentn Wodon and Shlomo Ytzha World Ban and Hebrew Unversty September Abstract Income nequalty typcally declnes wth the length of tme taen nto account for measurement.
More informationThe Greedy Method. Introduction. 0/1 Knapsack Problem
The Greedy Method Introducton We have completed data structures. We now are gong to look at algorthm desgn methods. Often we are lookng at optmzaton problems whose performance s exponental. For an optmzaton
More informations-domain Circuit Analysis
S-Doman naly -Doman rcut naly Tme doman t doman near rcut aplace Tranform omplex frequency doman doman Tranformed rcut Dfferental equaton lacal technque epone waveform aplace Tranform nvere Tranform -
More information1. Measuring association using correlation and regression
How to measure assocaton I: Correlaton. 1. Measurng assocaton usng correlaton and regresson We often would lke to know how one varable, such as a mother's weght, s related to another varable, such as a
More informationLecture 2: Single Layer Perceptrons Kevin Swingler
Lecture 2: Sngle Layer Perceptrons Kevn Sngler kms@cs.str.ac.uk Recap: McCulloch-Ptts Neuron Ths vastly smplfed model of real neurons s also knon as a Threshold Logc Unt: W 2 A Y 3 n W n. A set of synapses
More informationHow To Understand The Results Of The German Meris Cloud And Water Vapour Product
Ttel: Project: Doc. No.: MERIS level 3 cloud and water vapour products MAPP MAPP-ATBD-ClWVL3 Issue: 1 Revson: 0 Date: 9.12.1998 Functon Name Organsaton Sgnature Date Author: Bennartz FUB Preusker FUB Schüller
More informationBrigid Mullany, Ph.D University of North Carolina, Charlotte
Evaluaton And Comparson Of The Dfferent Standards Used To Defne The Postonal Accuracy And Repeatablty Of Numercally Controlled Machnng Center Axes Brgd Mullany, Ph.D Unversty of North Carolna, Charlotte
More informationwhere the coordinates are related to those in the old frame as follows.
Chapter 2 - Cartesan Vectors and Tensors: Ther Algebra Defnton of a vector Examples of vectors Scalar multplcaton Addton of vectors coplanar vectors Unt vectors A bass of non-coplanar vectors Scalar product
More informationn + d + q = 24 and.05n +.1d +.25q = 2 { n + d + q = 24 (3) n + 2d + 5q = 40 (2)
MATH 16T Exam 1 : Part I (In-Class) Solutons 1. (0 pts) A pggy bank contans 4 cons, all of whch are nckels (5 ), dmes (10 ) or quarters (5 ). The pggy bank also contans a con of each denomnaton. The total
More informationPSYCHOLOGICAL RESEARCH (PYC 304-C) Lecture 12
14 The Ch-squared dstrbuton PSYCHOLOGICAL RESEARCH (PYC 304-C) Lecture 1 If a normal varable X, havng mean µ and varance σ, s standardsed, the new varable Z has a mean 0 and varance 1. When ths standardsed
More informationAnswer: A). There is a flatter IS curve in the high MPC economy. Original LM LM after increase in M. IS curve for low MPC economy
4.02 Quz Solutons Fall 2004 Multple-Choce Questons (30/00 ponts) Please, crcle the correct answer for each of the followng 0 multple-choce questons. For each queston, only one of the answers s correct.
More information1. Fundamentals of probability theory 2. Emergence of communication traffic 3. Stochastic & Markovian Processes (SP & MP)
6.3 / -- Communcaton Networks II (Görg) SS20 -- www.comnets.un-bremen.de Communcaton Networks II Contents. Fundamentals of probablty theory 2. Emergence of communcaton traffc 3. Stochastc & Markovan Processes
More informationExtending Probabilistic Dynamic Epistemic Logic
Extendng Probablstc Dynamc Epstemc Logc Joshua Sack May 29, 2008 Probablty Space Defnton A probablty space s a tuple (S, A, µ), where 1 S s a set called the sample space. 2 A P(S) s a σ-algebra: a set
More informationHÜCKEL MOLECULAR ORBITAL THEORY
1 HÜCKEL MOLECULAR ORBITAL THEORY In general, the vast maorty polyatomc molecules can be thought of as consstng of a collecton of two electron bonds between pars of atoms. So the qualtatve pcture of σ
More informationThe Development of Web Log Mining Based on Improve-K-Means Clustering Analysis
The Development of Web Log Mnng Based on Improve-K-Means Clusterng Analyss TngZhong Wang * College of Informaton Technology, Luoyang Normal Unversty, Luoyang, 471022, Chna wangtngzhong2@sna.cn Abstract.
More informationRisk-based Fatigue Estimate of Deep Water Risers -- Course Project for EM388F: Fracture Mechanics, Spring 2008
Rsk-based Fatgue Estmate of Deep Water Rsers -- Course Project for EM388F: Fracture Mechancs, Sprng 2008 Chen Sh Department of Cvl, Archtectural, and Envronmental Engneerng The Unversty of Texas at Austn
More information21 Vectors: The Cross Product & Torque
21 Vectors: The Cross Product & Torque Do not use our left hand when applng ether the rght-hand rule for the cross product of two vectors dscussed n ths chapter or the rght-hand rule for somethng curl
More informationJ. Parallel Distrib. Comput.
J. Parallel Dstrb. Comput. 71 (2011) 62 76 Contents lsts avalable at ScenceDrect J. Parallel Dstrb. Comput. journal homepage: www.elsever.com/locate/jpdc Optmzng server placement n dstrbuted systems n
More informationHALL EFFECT SENSORS AND COMMUTATION
OEM770 5 Hall Effect ensors H P T E R 5 Hall Effect ensors The OEM770 works wth three-phase brushless motors equpped wth Hall effect sensors or equvalent feedback sgnals. In ths chapter we wll explan how
More informationUniversity Physics AI No. 11 Kinetic Theory
Unersty hyscs AI No. 11 Knetc heory Class Number Name I.Choose the Correct Answer 1. Whch type o deal gas wll hae the largest alue or C -C? ( D (A Monatomc (B Datomc (C olyatomc (D he alue wll be the same
More informationTime Domain simulation of PD Propagation in XLPE Cables Considering Frequency Dependent Parameters
Internatonal Journal of Smart Grd and Clean Energy Tme Doman smulaton of PD Propagaton n XLPE Cables Consderng Frequency Dependent Parameters We Zhang a, Jan He b, Ln Tan b, Xuejun Lv b, Hong-Je L a *
More informationForecasting the Direction and Strength of Stock Market Movement
Forecastng the Drecton and Strength of Stock Market Movement Jngwe Chen Mng Chen Nan Ye cjngwe@stanford.edu mchen5@stanford.edu nanye@stanford.edu Abstract - Stock market s one of the most complcated systems
More informationIT09 - Identity Management Policy
IT09 - Identty Management Polcy Introducton 1 The Unersty needs to manage dentty accounts for all users of the Unersty s electronc systems and ensure that users hae an approprate leel of access to these
More informationAn Evaluation of the Extended Logistic, Simple Logistic, and Gompertz Models for Forecasting Short Lifecycle Products and Services
An Evaluaton of the Extended Logstc, Smple Logstc, and Gompertz Models for Forecastng Short Lfecycle Products and Servces Charles V. Trappey a,1, Hsn-yng Wu b a Professor (Management Scence), Natonal Chao
More informationA Design Method of High-availability and Low-optical-loss Optical Aggregation Network Architecture
A Desgn Method of Hgh-avalablty and Low-optcal-loss Optcal Aggregaton Network Archtecture Takehro Sato, Kuntaka Ashzawa, Kazumasa Tokuhash, Dasuke Ish, Satoru Okamoto and Naoak Yamanaka Dept. of Informaton
More informationModule 2. AC to DC Converters. Version 2 EE IIT, Kharagpur 1
Module 2 AC to DC Converters erson 2 EE IIT, Kharagpur 1 Lesson 1 Sngle Phase Fully Controlled Rectfer erson 2 EE IIT, Kharagpur 2 Operaton and Analyss of sngle phase fully controlled converter. Instructonal
More informationIMPACT ANALYSIS OF A CELLULAR PHONE
4 th ASA & μeta Internatonal Conference IMPACT AALYSIS OF A CELLULAR PHOE We Lu, 2 Hongy L Bejng FEAonlne Engneerng Co.,Ltd. Bejng, Chna ABSTRACT Drop test smulaton plays an mportant role n nvestgatng
More informationLittle s Law & Bottleneck Law
Lttle s Law & Bottleneck Law Dec 20 I professonals have shunned performance modellng consderng t to be too complex and napplcable to real lfe. A lot has to do wth fear of mathematcs as well. hs tutoral
More informationEnabling P2P One-view Multi-party Video Conferencing
Enablng P2P One-vew Mult-party Vdeo Conferencng Yongxang Zhao, Yong Lu, Changja Chen, and JanYn Zhang Abstract Mult-Party Vdeo Conferencng (MPVC) facltates realtme group nteracton between users. Whle P2P
More informationStatistical Methods to Develop Rating Models
Statstcal Methods to Develop Ratng Models [Evelyn Hayden and Danel Porath, Österrechsche Natonalbank and Unversty of Appled Scences at Manz] Source: The Basel II Rsk Parameters Estmaton, Valdaton, and
More informationPAS: A Packet Accounting System to Limit the Effects of DoS & DDoS. Debish Fesehaye & Klara Naherstedt University of Illinois-Urbana Champaign
PAS: A Packet Accountng System to Lmt the Effects of DoS & DDoS Debsh Fesehaye & Klara Naherstedt Unversty of Illnos-Urbana Champagn DoS and DDoS DDoS attacks are ncreasng threats to our dgtal world. Exstng
More informationLogistic Regression. Lecture 4: More classifiers and classes. Logistic regression. Adaboost. Optimization. Multiple class classification
Lecture 4: More classfers and classes C4B Machne Learnng Hlary 20 A. Zsserman Logstc regresson Loss functons revsted Adaboost Loss functons revsted Optmzaton Multple class classfcaton Logstc Regresson
More informationHollinger Canadian Publishing Holdings Co. ( HCPH ) proceeding under the Companies Creditors Arrangement Act ( CCAA )
February 17, 2011 Andrew J. Hatnay ahatnay@kmlaw.ca Dear Sr/Madam: Re: Re: Hollnger Canadan Publshng Holdngs Co. ( HCPH ) proceedng under the Companes Credtors Arrangement Act ( CCAA ) Update on CCAA Proceedngs
More informationFINANCIAL MATHEMATICS. A Practical Guide for Actuaries. and other Business Professionals
FINANCIAL MATHEMATICS A Practcal Gude for Actuares and other Busness Professonals Second Edton CHRIS RUCKMAN, FSA, MAAA JOE FRANCIS, FSA, MAAA, CFA Study Notes Prepared by Kevn Shand, FSA, FCIA Assstant
More informationFisher Markets and Convex Programs
Fsher Markets and Convex Programs Nkhl R. Devanur 1 Introducton Convex programmng dualty s usually stated n ts most general form, wth convex objectve functons and convex constrants. (The book by Boyd and
More informationSimple Interest Loans (Section 5.1) :
Chapter 5 Fnance The frst part of ths revew wll explan the dfferent nterest and nvestment equatons you learned n secton 5.1 through 5.4 of your textbook and go through several examples. The second part
More informationtotal A A reag total A A r eag
hapter 5 Standardzng nalytcal Methods hapter Overvew 5 nalytcal Standards 5B albratng the Sgnal (S total ) 5 Determnng the Senstvty (k ) 5D Lnear Regresson and albraton urves 5E ompensatng for the Reagent
More informationTraffic State Estimation in the Traffic Management Center of Berlin
Traffc State Estmaton n the Traffc Management Center of Berln Authors: Peter Vortsch, PTV AG, Stumpfstrasse, D-763 Karlsruhe, Germany phone ++49/72/965/35, emal peter.vortsch@ptv.de Peter Möhl, PTV AG,
More informationFinancial Mathemetics
Fnancal Mathemetcs 15 Mathematcs Grade 12 Teacher Gude Fnancal Maths Seres Overvew In ths seres we am to show how Mathematcs can be used to support personal fnancal decsons. In ths seres we jon Tebogo,
More informationMODELING MEMORY ERRORS IN PIPELINED ANALOG-TO-DIGITAL CONVERTERS
MODELING MEMORY ERRORS IN PIPELINED ANALOG-TO-DIGITAL CONVERTERS John P. Keane, Paul J. Hurst, and Stephen H. Lews Dept. of Electrcal and Computer Eng. Unversty of Calforna, Davs, CA 9566, USA. emal: jpkeane@eee.org
More informationA Secure Password-Authenticated Key Agreement Using Smart Cards
A Secure Password-Authentcated Key Agreement Usng Smart Cards Ka Chan 1, Wen-Chung Kuo 2 and Jn-Chou Cheng 3 1 Department of Computer and Informaton Scence, R.O.C. Mltary Academy, Kaohsung 83059, Tawan,
More informationSolution: Let i = 10% and d = 5%. By definition, the respective forces of interest on funds A and B are. i 1 + it. S A (t) = d (1 dt) 2 1. = d 1 dt.
Chapter 9 Revew problems 9.1 Interest rate measurement Example 9.1. Fund A accumulates at a smple nterest rate of 10%. Fund B accumulates at a smple dscount rate of 5%. Fnd the pont n tme at whch the forces
More informationAddendum to: Importing Skill-Biased Technology
Addendum to: Importng Skll-Based Technology Arel Bursten UCLA and NBER Javer Cravno UCLA August 202 Jonathan Vogel Columba and NBER Abstract Ths Addendum derves the results dscussed n secton 3.3 of our
More informationProject Networks With Mixed-Time Constraints
Project Networs Wth Mxed-Tme Constrants L Caccetta and B Wattananon Western Australan Centre of Excellence n Industral Optmsaton (WACEIO) Curtn Unversty of Technology GPO Box U1987 Perth Western Australa
More informationForecasting the Demand of Emergency Supplies: Based on the CBR Theory and BP Neural Network
700 Proceedngs of the 8th Internatonal Conference on Innovaton & Management Forecastng the Demand of Emergency Supples: Based on the CBR Theory and BP Neural Network Fu Deqang, Lu Yun, L Changbng School
More informationSection 5.3 Annuities, Future Value, and Sinking Funds
Secton 5.3 Annutes, Future Value, and Snkng Funds Ordnary Annutes A sequence of equal payments made at equal perods of tme s called an annuty. The tme between payments s the payment perod, and the tme
More informationFuzzy Regression and the Term Structure of Interest Rates Revisited
Fuzzy Regresson and the Term Structure of Interest Rates Revsted Arnold F. Shapro Penn State Unversty Smeal College of Busness, Unversty Park, PA 68, USA Phone: -84-865-396, Fax: -84-865-684, E-mal: afs@psu.edu
More informationLevel Annuities with Payments Less Frequent than Each Interest Period
Level Annutes wth Payments Less Frequent than Each Interest Perod 1 Annuty-mmedate 2 Annuty-due Level Annutes wth Payments Less Frequent than Each Interest Perod 1 Annuty-mmedate 2 Annuty-due Symoblc approach
More informationSIMPLE LINEAR CORRELATION
SIMPLE LINEAR CORRELATION Smple lnear correlaton s a measure of the degree to whch two varables vary together, or a measure of the ntensty of the assocaton between two varables. Correlaton often s abused.
More informationOn some special nonlevel annuities and yield rates for annuities
On some specal nonlevel annutes and yeld rates for annutes 1 Annutes wth payments n geometrc progresson 2 Annutes wth payments n Arthmetc Progresson 1 Annutes wth payments n geometrc progresson 2 Annutes
More informationIn our example i = r/12 =.0825/12 At the end of the first month after your payment is received your amount in the account, the balance, is
Payout annutes: Start wth P dollars, e.g., P = 100, 000. Over a 30 year perod you receve equal payments of A dollars at the end of each month. The amount of money left n the account, the balance, earns
More informationDamage detection in composite laminates using coin-tap method
Damage detecton n composte lamnates usng con-tap method S.J. Km Korea Aerospace Research Insttute, 45 Eoeun-Dong, Youseong-Gu, 35-333 Daejeon, Republc of Korea yaeln@kar.re.kr 45 The con-tap test has the
More informationFault tolerance in cloud technologies presented as a service
Internatonal Scentfc Conference Computer Scence 2015 Pavel Dzhunev, PhD student Fault tolerance n cloud technologes presented as a servce INTRODUCTION Improvements n technques for vrtualzaton and performance
More informationA Performance Analysis of View Maintenance Techniques for Data Warehouses
A Performance Analyss of Vew Mantenance Technques for Data Warehouses Xng Wang Dell Computer Corporaton Round Roc, Texas Le Gruenwald The nversty of Olahoma School of Computer Scence orman, OK 739 Guangtao
More informationDescription of the Force Method Procedure. Indeterminate Analysis Force Method 1. Force Method con t. Force Method con t
Indeternate Analyss Force Method The force (flexblty) ethod expresses the relatonshps between dsplaceents and forces that exst n a structure. Prary objectve of the force ethod s to deterne the chosen set
More information