# 10-bit Σ ADC from a PIC16F84

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1 1-bit Σ ADC from a PIC16F84 Jesús Arias 22nd November 23 1 The circuit +5V 1 + 1uF 1nF 1nF V DTR U1 Analog Input ( 5 Volt) R3 68K R1 1K R2 1K C1 33nF PIC16F84 RB7 RA2 RA3 ad2.asm OSC1 OSC2 X1 R4 22K R5 1K Q1 BC557 RXD CTS GND 4MHz The schematic of the ADC consist mainly of a PIC16F84 microcontroller and a RC network. The microcontroller generates an RS232-compatible output (96 baud, 8 bit, no parity) thanks to the level-converter circuit that is shown on the right of the schematic. The PIC16F84 must be clocked at 4 MHz. The ratio between R1 and R2 defines the input range of the converter: V in R2 R1 V dd The resistor R3 is used to adjust the input offset. The center-of-scale code is obtained for the following input voltage: V dd R1 V in V th 2 R2 1 R1 R2 R1 R3 were V th is the threshold voltage of the input pin (RA3). In our case V dd is 5 volts and V th is about 1.4 volts (from PIC16F84 datasheet). Alternatively, if we want our input range centered around V dd 2, the R3 value must be: 1

2 R3 R1 R2 V th V dd 2 V th The resistor values in this design give an input range of 5 volts centered around 2.5 volts. The Σ conversion works generating a train of pulses on the pin RA2 whose average value cancels the input signal at the capacitor node. This forces a voltage at pin RA3 very close to the pin threshold. The program running in the PIC microcontroller generates the output pulses by just inverting the logic level of pin RA3 every 14 µs and copying it into the RA2 output. These pulses are recorded and they are used to reconstruct the equivalent input voltage by doing a digital filtering. A good, regulated, power supply is required. Decoupling capacitors must be close to microcontroller power pins. In addition, we must avoid loading other microcontroller s pins. e.g. It would be a bad idea to drive a LED directly from a microcontroller pin. If other pins are used as outputs they must be isolated using a buffer powered from a different voltage source in order to maintain the microcontroller power supply clean. 2 The digital filter The filtering of the Σ modulator stream is done by program. The filter used is a second-order comb filter, whose structure is: decimation RA2 1 Z 1 Z Z 1 1 Z 1 aout comb comb1 comb2 comb3 This filter is composed of two integrators, running at 96 Hz, followed by sample decimation and two differentiators running at Hz. The filter input is only one bit, but each comb variable is 16 bits long and so it is the output. It must be noted that, even if the output samples are 16-bit long, the less-significant bits are almost random. The expected AD resolution is only 1 bits. The data processing is done in an interrupt routine using 16-bit integer arithmetic (A pain in the neck for a CPU without ADD-with-carry instructions). 3 Simulation results The following results were obtained using the f84 simulator conveniently modified to simulate the analog section on the prototype and its serial output. 2

4 tone. This means that the signal distortion is less than the ADC noise, and, therefore, we can state that this is a very linear converter. The FFT length was 228 samples. 4 The program The microcontroller program is written in native assembly language. It requires 166 words of flash memory for the program itself and 31 bytes of RAM for variables. Interrupts are called every 14 clock cycles. A typical interruption takes 39 cycles to execute, but every 256 interrupts we have a longer interruption that takes 67 clock cycles. The AD conversion accounts for a 37% of the total CPU time. 5 Program listing ; ; This program is distributed under GNU GPL license ; processor p16f84 config x3ff2 radix dec w equ f equ 1 c equ dc equ 1 z equ 2 indf equ x tmr equ x1 pcl equ x2 status equ x3 fsr equ x4 porta equ x5 portb equ x6 eedata equ x8 eeadr equ x9 pclatch equ xa intcon equ xb optionr equ x81 trisa equ x85 trisb equ x86 eecon1 equ x88 eecon2 equ x89 ; ; Variable defs. 4

5 ; cblock xc tmp_w tmp_st nirq nsamples sampleix comb combh comb1 comb1h comb2 comb2h comb3 comb3h aout aouth adata adata_h nchar resto cntbit obyte uart uarth uartdel tmp buf endc ; RESET ; Configuration: ; ; RA3 A/D input ; RA2 A/D output ; RB7 UART output ; org movlw xfb ;RA2 out tris porta goto ini ; INTERRUPT (9615/sec) org x4 5

6 tmp_w ;save CPU status swapf status,w tmp_st bcf intcon,2 ;clear interrupt ;Interrupt latency equalization (to add 1-cycle delay if needed) ; - can give 3 db improvement (1/2 bit) ; Some experimentation is still needed because ; PIC16F84 interrupt details are not well known ;We can try: ; - No equalization ; - btfsc tmr, ; - btfss tmr, btfsc tmr, goto deleq deleq movlw ;adjust timer for a new addwf tmr,f ;interrupt ; A/D rrf porta,w ;A/D feedback loop xorlw 4 ;~RA3 -> RA2 porta ;---- UART ---- ;16-bit shift reg. bsf status,c rrf uarth,f rrf uart,f btfsc status,c bsf portb,7 btfss status,c bcf portb,7 uartdel,f ;dec. uartdel if not btfss status,z decf uartdel ;---- Comb Filter: integrators ---- btfsc porta,2 goto isr1 incfsz comb,f goto isr1 incf combh,f isr1 comb,w addwf comb1,f btfsc status,c incf comb1h,f 6

7 addwf combh,w comb1h,f ;----- DECIMATION: The differentiator code is called ;----- every 256 interrupts incfsz nirq,f goto isrf ;----- Comb Filter: differentiators ; aout =comb1-comb2-comb3 ; comb3=comb1-comb2 ; comb2=comb1 subwf btfss decf subwf subwf btfss decf subwf incf comb1,w aout comb1h,w aouth comb2,w aout,f status,c aouth,f comb2h,w aouth,f aout,w comb2 aouth,w comb2h comb3,w aout status,c aouth,f comb3h,w aouth,f comb2,w comb3 comb2h,w comb3h comb1,w comb2 comb1h,w comb2h nsamples,f 7

8 ;---- End of Interrupt ---- isrf swapf tmp_st,w ;restore cpu status status swapf tmp_w,f swapf tmp_w,w retfie ; ; MAIN ; ini movlw x7e ;RB7, RB out tris portb movlw x88 ;No Pull-UPs, no prescaler option clrf nirq ;Clearing variables clrf nsamples clrf sampleix clrf comb clrf combh clrf comb1 clrf comb1h clrf comb2 clrf comb2h clrf comb3 clrf comb3h movlw xff uart uarth bsf portb,7 ; Default state of UART s line movlw xa ; Interrupt on timer overflow intcon buc call getad ; get AD sample call prtn ; And print it in decimal goto buc ; UART EMULATOR (96 bps) ; Sends the byte: "obyte" ; putbyte nirq,w tmp 8

9 pbbuc1 tmp,w ;wait until next interrupt subwf nirq,w btfsc status,z goto pbbuc1 pbbuc2 uartdel,f btfss status,z goto pbbuc2 movlw xff ; Filling the UART shift reg. uarth obyte,w uart bcf status,c rlf uart rlf uarth movlw 1 ; Wait until 1 interrupts uartdel return ; BIN to ASCII ; divide by 1: adata(16 bits)/1 -> adata,resto ; div1 movlw 16 cntbit clrf resto movlw 1 bdiv1 bcf status, rlf adata,f rlf adata_h,f rlf resto,f subwf resto,f btfsc status,c incf adata btfss status,c addwf resto,f decfsz cntbit,f goto bdiv1 retlw ; ;-- prtn: prints adata (16 bits) in ascii ;

10 prtn movlw buf fsr clrf nchar bprtn1 call div1 incf nchar resto,w addlw 48 indf incf fsr adata,w iorwf adata_h,w btfss status,z goto bprtn1 bprtn2 decf fsr,f indf,w obyte call putbyte decfsz nchar,f goto bprtn2 movlw 1 obyte call putbyte retlw ; ; A/D read: new sample -> adata ; getad nsamples,w subwf sampleix,w btfsc status,z goto getad nsamples,w sampleix aout,w adata aouth,w adata_h bsf portb, ; Pulse on PB for timming debug bcf portb, return 6 Experimental results The proposed ADC was built and tested. First, in order to test the basic operation of the converter, an exponential ramp was applied to the input from a big capacitor that was charged from ground to +5V through a resistor. The recorded transient is shown in Fig 1. 1

11 65536 RC-transient test ADC code sample # Figure 1: Transient signal recorded using the proposed ADC. Then, by cropping the exponential part of the transient and by doing a nonlinear curve fitting we obtained the average error of the converter (Fig 2). This plot shows a different behavior than predicted from simulations, with an average error about 1 1-bit LSB and with higher peak values. The peaks in this plot are due to idle tones in the converter, a well known problem of first-order delta-sigma modulators. Finally, a 4.7 Hz sinusoid was applied to the input and the recorded data stream was processed in the frequency domain using a Fourier transform. The obtained spectrum is shown in Fig 3. The measured SNR was 64 db (1.3 effective bits) and the total harmonic distortion was -61 db. 11

12 INL (1-bit LSB) ADC code Figure 2: Nonlinearity plot of the ADC. SNR = 64 db, THD = -61 db -2-4 Ampl. (db) Freq. (Hz) Figure 3: Spectrum of a digitized sinusoid. (496-sample FFT) 12

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