TM MP2305 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER

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1 The Future of Analog IC Technology TM TM MP305 A, 3 Synchronous Rectified Step-Down Converter DESCRIPTION The MP305 is a monolithic synchronous buck regulator. The device integrates 30mΩ MOSFETS that provide A continuous load current over a wide operating input voltage of 4.75 to 3. Current mode control provides fast transient response and cycle-by-cycle current limit. An adjustable soft-start prevents inrush current at turn-on. Shutdown mode drops the supply current to µa. This device, available in an 8-pin SOIC package, provides a very compact system solution with minimal reliance on external components. EALUATION BOARD REFERENCE Board Number Dimensions E305DS-00A.0 X x.5 Y x 0.5 Z FEATURES A Output Current Wide 4.75 to 3 Operating Input Range Integrated 30mΩ Power MOSFET Switches Output Adjustable from 0.93 to 0 Up to 93% Efficiency Programmable Soft-Start Stable with Low ESR Ceramic Output Capacitors Fixed 340KHz Frequency Cycle-by-Cycle Over Current Protection Input Under oltage Lockout APPLICATIONS Distributed Power Systems Networking Systems FPGA, DSP, ASIC Power Supplies Green Electronics/ Appliances Notebook Computers MPS and The Future of Analog IC Technology are Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION PUT 4.75 to EN SS GND 4 BS 3 SW MP305 5 FB COMP C6 (optional) 6 C3 3.3nF C5 0nF D B30 (optional) PUT 3.3 A MP305-TAC0 EFFICIENCY (%) Efficiency vs Load Current = = LOAD CURRENT (A) MP305-EC0 MP305 Rev..3 0/3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

2 PACKAGE REFERENCE BS SW GND 3 4 TOP IEW SS EN COMP FB MP305_PD0 Part Number* Package Temperature MP305DS SOIC8 40 to 85 C * For Tape & Reel, add suffix Z (eg. MP305DS Z) For Lead Free, add suffix LF (eg. MP305DS LF Z) ABSOLUTE MAXIMUM RATGS () Supply oltage to 6 Switch oltage SW... to 0.3 Boost oltage BS... SW 0.3 to SW 6 All Other Pins to 6 Junction Temperature...50 C Lead Temperature...60 C Storage Temperature C to 50 C Recommended Operating Conditions () Input oltage to 3 Output oltage to 0 Ambient Operating Temperature C to 85 C Thermal Resistance (3) θ JA θ JC SOIC C/W Notes: ) Exceeding these ratings may damage the device. ) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately square of oz copper. ELECTRICAL CHARACTERISTICS =, T A = 5 C, unless otherwise noted. Parameter Symbol Condition Min Typ (4) Max Units Shutdown Supply Current EN = µa Supply Current EN =.0; FB = ma Feedback oltage FB Feedback Overvoltage Threshold. Error Amplifier oltage Gain A EA 400 / Error Amplifier Transconductance G EA I C = ±0µA 800 µa/ High Side Switch On Resistance R DS(ON) 30 mω Low Side Switch On Resistance R DS(ON) 30 mω High Side Switch Leakage Current EN = 0, SW = 0 0 µa Upper Switch Current Limit Minimum Duty Cycle 3.4 A Lower Switch Current Limit From Drain to Source. A COMP to Current Sense Transconductance G CS 3.5 A/ Oscillation Frequency F osc 340 KHz Short Circuit Oscillation Frequency F osc FB = 0 00 KHz Maximum Duty Cycle D MAX FB =.0 90 % Minimum On Time 0 ns EN Shutdown Threshold oltage EN Rising..3.5 EN Shutdown Threshold oltage Hysterisis 0 m EN Lockout Threshold oltage..5.7 EN Lockout Hysterisis 0 m MP305 Rev..3 0/3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

3 ELECTRICAL CHARACTERISTICS (continued) =, T A = 5 C, unless otherwise noted. Parameter Symbol Condition Min Typ (4) Max Units Input Under oltage Lockout Threshold Rising Input Under oltage Lockout Threshold Hysteresis 0 m Soft Start Current SS = 0 6 µa Soft Start Period C SS = 0.µF 5 ms Thermal Shutdown 60 C Note: 4) Guaranteed by design, not tested. P FUNCTIONS Pin # Name Description BS High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.0µF or greater capacitor from SW to BS to power the high side switch. Power Input. supplies the power to the IC, as well as the step-down converter switches. Drive with a 4.75 to 3 power source. Bypass to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. 3 SW Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. 4 GND Ground. 5 FB 6 COMP 7 EN 8 SS Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive voltage divider from the output voltage. The feedback threshold is See Setting the Output oltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND to compensate the regulation control loop. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator, drive it low to turn it off. Pull up with 00kΩ resistor for automatic startup. Soft-Start Control Input. SS controls the soft start period. Connect a capacitor from SS to GND to set the soft-start period. A 0.µF capacitor sets the soft-start period to 5ms. To disable the soft-start feature, leave SS unconnected. MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

4 TYPICAL PERFORMANCE CHARACTERISTICS =, O = 3.3, L = 0µH, C = 0µF, C = µf, T A = 5 C, unless otherwise noted. Steady State Test =, = 3.3, I = 0A, I =8. ma Start-up through Enable =, = 3.3, I = A (Resistance Load) Shut-down through Enable =, = 3.3, I = A (Resistance Load) MP305-TPC0 ms/div. MP305-TPC0 ms/div. MP305-TPC03 Heavy Load Operation A Load Medium Load Operation A Load Light Load Operation No Load,AC 00m/div.,AC 00m/div.,AC 0m/div. O,AC 0m/div. O,AC 0m/div. O,AC 0m/div. A/div. A/div. A/div. SW 0/div. SW 0/div. SW 0/div. MP305-TPC04 MP305-TPC05 MP305-TPC06 Short Circuit Protection Short Circuit Recovery Load Transient /div. /div. O,AC 00m/div. A/div. A/div. A/div. OAD A/div. MP305-TPC07 MP305-TPC08 MP305-TPC09 MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

5 OPERATION FUNCTIONAL DESCRIPTION The MP305 is a synchronous rectified, current-mode, step-down regulator. It regulates input voltages from 4.75 to 3 down to an output voltage as low as 0.93, and supplies up to A of load current. The MP305 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at the COMP pin is compared to the switch current measured internally to control the output voltage. The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high side gate. The boost capacitor is charged from the internal 5 rail when SW is low. When the MP305 FB pin exceeds 0% of the nominal regulation voltage of 0.93, the over voltage comparator is tripped and the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off. FB OP OSCILLATOR 00/340KHz RAMP CLK S CURRENT SENSE AMPLIFIER Q 5 BS SS ERROR AMPLIFIER R Q CURRENT COMPARATOR 3 SW COMP 6.5 EN OK. EN 4 GND OP < 4.0 LOCK COMPARATOR EN 7.3 SHUTDOWN COMPARATOR TERNAL REGULATORS 5 MP305_F0_BD0 Figure Functional Block Diagram MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

6 APPLICATIONS FORMATION COMPONENT SELECTION Setting the Output oltage The output voltage is set using a resistive voltage divider from the output voltage to FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: R FB = R R Where FB is the feedback voltage and is the output voltage. Thus the output voltage is: R R = 0.93 R R can be as high as 00kΩ, but a typical value is 0kΩ. Using the typical value for R, R is determined by: R = 0.83 ( 0.93) (kω) For example, for a 3.3 output voltage, R is 0kΩ, and R is 6.kΩ. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: L = fs IL Where is the output voltage, is the input voltage, f S is the switching frequency, and is the peak-to-peak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: P = ILOAD fs L Where OAD is the load current. The choice of which style inductor to use mainly depends on the price vs. size requirements and any EMI requirements. Optional Schottky Diode During the transition between high-side switch and low-side switch, the body diode of the lowside power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table lists example Schottky diodes and their Manufacturers. Table Diode Selection Guide Part Number oltage/current Rating endor B30 30, A Diodes, Inc. SK3 30, A Diodes, Inc. MBRS30 30, A International Rectifier Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-esr electrolytic capacitors may also suffice. Choose X5R or X7R dielectrics when using ceramic capacitors. Since the input capacitor absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: I C = I LOAD MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

7 The worst-case condition occurs at =, where I C = OAD /. For simplification, choose the input capacitor whose RMS current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.µF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple for low ESR capacitors can be estimated by: ILOAD = C fs Where C is the input capacitance value. Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: = RESR f S L 8 fs CO Where C O is the output capacitance value and R ESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is mainly caused by the capacitance. For simplification, the output voltage ripple can be estimated by: = 8 fs L CO In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: = R fs L ESR The characteristics of the output capacitor also affect the stability of the regulation system. The MP305 can be optimized for a wide range of capacitance and ESR values. Compensation Components MP305 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP pin is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by: A DC = RLOAD GCS A EA FB Where A EA is the error amplifier voltage gain; G CS is the current sense transconductance and R LOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of the error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: f f P P GEA = π C3 A = π C R O EA LOAD Where G EA is the error amplifier transconductance. The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: f Z = π C3 R3 The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: f ESR = π C R O ESR MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

8 In this case (as shown in Figure ), a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at: f P 3 = π C6 R3 The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good rule of thumb is to set the crossover frequency below one-tenth of the switching frequency. To optimize the compensation components, the following procedure can be used.. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation: π CO fc π CO 0. fs R 3 = < GEA GCS FB GEA GCS FB Where f C is the desired crossover frequency which is typically below one tenth of the switching frequency.. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, f Z, below one-forth of the crossover frequency provides sufficient phase margin. Determine the C3 value by the following equation: 4 C3 > π R3 f C 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the switching frequency, or the following relationship is valid: π C O R f < S ESR If this is the case, then add the second compensation capacitor (C6) to set the pole f P3 at the location of the ESR zero. Determine the C6 value by the equation: C RESR C6 = R3 External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5 fixed input or the power supply generates a 5 output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as 448 or BAT54. MP305 BS SW O 5 0nF MP305_F0 Figure External Bootstrap Diode This diode is also recommended for high duty cycle operation (when >65%) and high output voltage ( >) applications. Where R3 is the compensation resistor. MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

9 PACKAGE FORMATION SOIC8 P IDENT. 0.9(5.80) 0.44(6.00) 0.50(3.80) 0.57(4.000) (0.9) (0.49) SEE DETAIL "A" 0.03(0.330) 0.00(0.508) 0.050(.70)BSC 0.0(0.80) 0.00(0.508) x 45o 0.053(.350) 0.068(.730) 0.89(4.800) 0.97(5.004) 0.049(.50) 0.060(.54) 0.00(0.030) 0.004(0.0) SEATG PLANE 0 o -8 o 0.06(0.40) DETAIL "A" 0.050(.70) NOTE: ) Control dimension is in inches. Dimension in bracket is millimeters. NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP305 Rev /3/005 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

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