TOP VIEW 16 ON OUTPUT 3.3V/5V C3 SO

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1 ; Rev 0; 7/97 EALUATION KIT MANUAL FOLLOWS DATA SHEET 3.3/5 or Adjustable, General Description The integrate a step-up DC-DC converter with a linear regulator to provide step-up/down voltage conversion. They are optimized for battery applications where the input varies above and below the regulated output voltage. They have an input range from +1.8 to +11. Typical efficiency when boosting battery inputs is 85%. The can be configured for minimum noise or optimum efficiency. Shutdown control turns off the part completely, disconnecting the input from the output (I = 0.2µA). Standby control turns off only the step-up converter and leaves the low-power linear regulator active (IQ = 7µA). The MAX710 has a preset 3.3 or 5 output voltage. The MAX711 has an adjustable output that can be set from +2.7 to +5.5 with two resistors. Both devices come in 16-pin narrow SO packages. Applications Single-Cell, Lithium-Powered Portable Devices Digital Cameras 2- to 4-Cell AA Alkaline Hand-Held Equipment 3.3 and Other Low-oltage Systems 2-, 3-, and 4-Cell Battery-Powered Equipment Battery-Powered Devices with AC Input Adapters Features Step-Up/Down oltage Conversion +1.8 to +11 Input Range Output: 5/250mA at IN = 1.8 5/500mA at IN = 3.6 No External FETs Required Load Disconnected from Input in Shutdown Battery Drain: 200µA No-Load ( IN = 4) 7µA in Standby 0.2µA when Off Low-Noise and High-Efficiency Modes Ordering Information PART TEMP. RANGE PIN-PACKAGE MAX710C/D MAX710ESE MAX711C/D 0 C to +70 C -40 C to +85 C 0 C to +70 C Dice 16 Narrow SO Dice MAX711ESE -40 C to +85 C 16 Narrow SO Typical Operating Circuit Pin Configuration +1.8 TO +11 INPUT TOP IEW C1 L ON 3.3 OFF ON 5 GND 3/5 MAX710 C4 C2 PUT 3.3/5 3/5 (FB) MAX710 MAX GND 8 9 C3 0.1µF SO ( ) IS FOR THE MAX711. Maxim Integrated Products 1 For free samples & the latest literature: or phone For small orders, phone ext

2 ABSOLUTE MAXIMUM RATINGS,, to GND to +11.5,,, FB, 3/5,,,,, to GND to ( + 0.3) to GND to +0.3 Short Circuit to GND...Continuous I...700mA Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ELECTRICAL CHARACTERISTICS Continuous Power Dissipation (T A = +70 C) SO (derate 8.70mW/ C above +70 C)...696mW Operating Temperature Range C to +85 C Storage Temperature Range C to +160 C Junction Temperature C Lead Temperature (soldering, 10sec) C ( = 5.6, =, C = 0.1µF, C = 4.7µF, T A = -40 C to +85 C, unless otherwise noted. Typical values are at T A = +25 C.) (Note 1) Input oltage Full Load Start-Up oltage Output oltage-adjustment Range Quiescent Current Reference oltage FB oltage PARAMETER Output oltage (MAX710) Output oltage Load Regulation Output oltage Line Regulation Standby Quiescent Current Shutdown Quiescent Current Standby Output Current = = GND (Note 2) 3/5 = low, I = 0 to 250mA 3/5 = high, I = 0 to 250mA, = 4.7 MAX711 = = logic high, current measured into pin; I LOAD = 0 = 0 = 0 T A = 0 C to +85 C, I = 0 T A = -40 C to +85 C, I = 0 = 0, linear regulator MAX711, = FB CONDITIONS T A = 0 C to +85 C T A = -40 C to +85 C T A = 0 C to +85 C T A = -40 C to +85 C T A = 0 C to +85 C T A = -40 C to +85 C MIN TYP MAX FB UNITS 0 < I < 250mA, = 0.5 % =, 1.8 to %/ µa µa µa ma m Load Regulation FB Input Current FB = 1.25 = 5.6 On-Resistance MAX710, = Leakage Current Current Limit 0mA I LOAD MAX711, = FB % 250mA MAX711, = 2.7 = 5.6 = = GND na Ω µa A 2

3 ELECTRICAL CHARACTERISTICS (continued) ( = 5.6, =, C = 0.1µF, C = 4.7µF, T A = -40 C to +85 C, unless otherwise noted. Typical values are at T A = +25 C.) (Note 1) Thermal Shutdown Input Low oltage PARAMETER Output PFET Resistance Output PFET Leakage Thermal Shutdown Hysteresis LOGIC Input High oltage Input Bias Current LBI/ COMPARATOR Input Range, Input Bias Current, Hysteresis LBI/ Offset oltage Output oltage = 5.0 = CONDITIONS,,, 3/5,,,, 3/5,,,, 3/5, (Note 3), = 1.25 = 1.25 I = 2mA, = 1.25, = 1 I = -300µA, = 1.25, = 2 MIN TYP MAX Note 1: Specifications at -40 C are guaranteed by design, not production tested. Note 2: Guaranteed by design (see Table 1). Note 3: The comparator provides the correct result as long as one input is within the specified input range MAX710, = MAX711, = UNITS = 3, = µa = 20 C Ω C na na m m 3

4 Typical Operating Characteristics (T A = +25 C, unless otherwise noted.) EFFICIENCY (%) EFFICIENCY vs. PUT CURRENT HIGH-EFFICIENCY MODE ( = 5) IN = 5.6 IN = 3.6 IN = 2.5 IN = 1.8 IN = 1 = 5 = GND PUT CURRENT (ma) MAX710/711 TOC01 EFFICIENCY (%) EFFICIENCY vs. PUT CURRENT HIGH-EFFICIENCY MODE ( = 3.3) IN = 2.5 IN = 1.8 IN = 1 = 3.3 = GND PUT CURRENT (ma) MAX710/711 TOC02 INPUT OLTAGE () MINIMUM START-UP INPUT OLTAGE vs. LOAD CURRENT = 5 = LOAD CURRENT (ma) MAX710/711 TOC03 EFFICIENCY (%) EFFICIENCY vs. LOAD CURRENT HIGH-EFFICIENCY AND LOW-NOISE MODES ( = 5) = GND = = 1.5A = 0.8A = 5 IN = LOAD CURRENT (ma) MAX710/711 TOC04 EFFICIENCY (%) EFFICIENCY vs. LOAD CURRENT HIGH-EFFICIENCY AND LOW-NOISE MODES ( = 3.3) HIGH-EFFICIENCY MODE = 0.8A = 1.5A = 0.8A = 1.5A LOW-NOISE MODE = 3.3 IN = LOAD CURRENT (ma) MAX710/711 TOC05 SUPPLY CURRENT (µa) NO-LOAD BATTERY CURRENT vs. INPUT OLTAGE = (0.8A) = GND (1.5A) = GND INPUT OLTAGE () MAX710/711 TOC06 MAXIMUM PUT CURRENT (ma) MAXIMUM PUT CURRENT vs. INPUT OLTAGE = GND = = GND = MAX710/711 TOC07 RR (db) LINEAR-REGULATOR POWER-SUPPLY REJECTION RATIO vs. FREQUENCY MAX710/711 TOC08 SHUTDOWN CURRENT (µa) SHUTDOWN CURRENT vs. INPUT OLTAGE MAX710/711 TOC INPUT OLTAGE () FREQUENCY (khz) INPUT OLTAGE () 4

5 Typical Operating Characteristics (continued) (T A = +25 C, unless otherwise noted.) LINE-TRANSIENT RESPONSE 2ms/div A: = 3.3 (100m/div, AC COUPLED), = GND B: IN = 2 TO 4, I = 100mA MAX710/711 TOC10 A B LOAD-TRANSIENT RESPONSE 1ms/div A: = 3.3 (50m/div, AC COUPLED), = B: I = 10mA TO 100mA MAX710/711 TOC11 A B PUT RIPPLE (HIGH-EFFICIENCY MODE) MAX710/711 TOC12 PUT RIPPLE (LOW-NOISE MODE) MAX710/711 TOC13 200µs/div IN = 2.5, I = 20mA, = GND = 5 (20m/div, AC COUPLED), I = 20mA START-UP DELAY MAX710/711 TOC14 200µs/div IN = 2.5, I = 20mA, = = 5 (20m/div, AC COUPLED), I = 20mA TURN-OFF DELAY MAX710/711 TOC15 A A B B 20µs/div A: (2/div), I = 100mA B: (2/div) A: (2/div), I = 100mA B: (2/div) 200µs/div 5

6 Pin Description MAX PIN MAX NAME 3/5 FB GND Drain Connection for internal N-channel power MOSFET Power Ground Inductor Current-Limit-Select Input. Connect to GND for 1.5A limit and to for 0.8A limit. Shutdown Input. When low, the entire circuit is off and is actively pulled to GND. Standby Input. Connect to GND to disable boost circuit. Connect to for normal operation. Selects the output voltage. Connect to GND for 5 output and to for 3.3 output. Feedback Input Selects low-noise or high-efficiency mode. Connect to GND for high efficiency and to for lowest noise. See Operating Configurations section. Low-Battery Comparator Output Linear-Regulator Output. Bypass with a 4.7µF capacitor to GND. Negative Input to Low-Battery Comparator Positive Input to Low-Battery Comparator Source of internal PFET regulator. The IC is powered from Reference oltage Output. Bypass with a 0.1µF capacitor to GND. Analog Ground. Must be low impedance. Solder directly to ground plane. Power Ground FUNCTION Drain Connection for internal N-channel power MOSFET Detailed Description The integrate a step-up DC-DC converter with a linear regulator to provide step-up/down voltage conversion. The step-up switch-mode regulator contains an N-channel power MOSFET switch. It also shares a precision voltage reference with a linear regulator that contains a P-channel MOSFET pass element (Figure 1). Step-Up Operation A pulse-frequency-modulation (PFM) control scheme with a constant 1µs off-time and variable on-time controls the N-channel MOSFET switch. The N-channel switch turns off when the part reaches the peak current limit or the 4µs maximum on-time. The ripple frequency is a function of load current and input voltage. Step-Down Operation The low-dropout linear regulator consists of a reference, an error amplifier, and a P-channel MOSFET. The reference is connected to the error amplifier s inverting input. The error amplifier compares this reference with the selected feedback voltage and amplifies the difference. The difference is conditioned and applied to the P-channel pass transistor s gate. Operating Configurations The have several operating configurations to minimize noise and optimize efficiency for different input voltage ranges. These configurations are accomplished via the input, which controls operation of the on-chip linear regulator. With low, the linear regulator behaves as a 0.7Ω (at 5 output) PFET switch when the IC is boosting, and as a conventional linear regulator when IN >. This provides optimum boost efficiency, but the PFET does little to reject boost-converter output ripple. With high, boost ripple rejection is optimized by maintaining headroom (F, typically 0.5 at 5 output) across the linear regulator. Boost mode efficiency is then about 10% lower than with high. 6

7 1 F MAX710 ERROR AMP2 OFF t ON FIXED t OFF GENERATOR CURRENT- LIMIT COMPARATOR 100m DR N IN 1 ERROR AMP1 2 (FB) A 2 3.3/5 B 1 GND ( ) IS FOR MAX711. Figure 1. Functional Diagram 7

8 In high-efficiency mode ( = low), the maximum input voltage is limited to 7. This voltage limitation is easily overcome, however, by configuring the output to change modes based on input voltage, allowing an 11 maximum input with high-efficiency configurations. Four operating configurations are described in Table 1 and in the following subsections. Table 1. Operating Configurations NO DESCRIPTION High efficiency, 7 max IN High efficiency, BATT < (Figure 2a) High efficiency, 11, BATT < 6.5 (Figure 2b) Low noise INPUT OLTAGE Up to 7 Up to 11 Up to 11 Up to 11 CONNECTIONS = GND = = = IN = = = R5, R6 = Configuration 1: High Efficiency, 7 Max IN With connected to GND, when the IC boosts, the linear regulator operates only as a switch, with minimum forward drop, until IN > (where linear regulation begins). This configuration is limited to no more than 7 input, but provides best efficiency for batteryonly operation or low-voltage AC adapter usage. Configuration 2: High Efficiency, BATT < In this configuration, is driven high by when IN > (Figure 2a). When IN <, the IC boosts, and the linear regulator operates as a switch, with minimum forward drop. When IN >, the linear regulator operates with F forward drop, while increases by F so that maintains regulation. F is set inside the IC to approximately 0.5 (at 5 ). When IN is only slightly higher than, conversion efficiency is poorer than in configuration 1, so configuration 2 is most suitable when the battery voltage is less than, but the AC adapter output is greater than. IN = +1.8 TO +11 IN = +1.8 TO µF L1 100µF L1 100µF 100µF MAX µF R5 MAX µF GND 3/5 R6 0.1µF 0.1µF GND 3/5 R5 = R6 ( IN - ) R5 = R6 (4.08) WHEN = 1.28 AND IN = 6.5 Figure 2a. High-Efficiency Operating Configuration for BATT < Figure 2b. High-Efficiency Operating Configuration for BATT < 6.5 8

9 Configuration 3: High Efficiency, 11, BATT < 6.5 In this configuration, is driven high by when IN > 6.5 (Figure 2b). When IN <, the IC boosts, and the linear regulator operates as a switch, with minimum forward drop. When IN >, linear regulation begins. When IN > 6.5 (set by R5 and R6), the linear regulator forces a minimum forward drop of F (typically 0.5 at 5 ) as drives high. This transition is not seen at the output, since the linear regulator already has an input-output voltage difference of Efficiency with IN slightly higher than is equal to that of configuration 1, so configuration 3 is most suitable when the battery voltage may be near. This hookup has no functional shortcomings compared with configuration 2, except that two additional resistors (R5 and R6) are needed. Configuration 4: Low Noise With connected to, when the IC is boosting, the linear regulator operates with F forward voltage (typically 0.5 at 5 ) for optimum noise rejection. Linear regulation occurs when IN > + F. The F voltage differential results in boost efficiency typically 10% lower than with the high-efficiency configurations. The current-limit-select input,, selects between the two peak current limits: 1.5A ( = GND) and 0.8A ( = ). If the application requires 200mA or less from the, select 0.8A. The lower peak current limit permits the use of smaller, low-cost inductors. The input is internally diode clamped to GND and, and should not be connected to signals outside this range. Shutdown and Standby Modes Grounding turns off the completely, disconnecting the input from the output. Tie to for normal operation. The have a standby mode that shuts down the step-up converter. The linear regulator remains on with a 7µA (typ) LDO quiescent current. Connect to ground to enter standby mode; otherwise, connect to. Design Procedure Output oltage Selection For the MAX710, you can obtain a 3.3 or 5 output voltage by tying 3/5 to GND or. Efficiency is typically 85% over a 2mA to 250mA load range. The device is bootstrapped, with power derived from the step-up voltage output (at ). Under all load conditions, the IN C1 R3 R4 ON OFF MAX711 typically start up with a 1 input. If the battery voltage exceeds the programmed output voltage, the output will linear regulate down to the selected output voltage. The MAX711 s adjustable output voltage is set by two resistors, R1 and R2 (Figure 3), which form a voltage divider between the output and FB. Use the following equation to determine the resistor values: R1 = R2 [( / ) - 1] where = Since the input bias current at FB has a maximum value of 50nA, R1 and R2 can be large with no significant accuracy loss. Choose R2 in the 100kΩ to 1MΩ range and calculate R1 using the formula above. For 1% error, the current through R1 should be at least 100 times FB s bias current. Low-Battery Comparator The contain a comparator for lowbattery detection. If the voltage at falls below that at (typically connected to ), goes low. Hysteresis is typically 50m. Set the low-battery monitor s threshold with two resistors, R3 and R4 (Figure 2), using the following equation: R3 = R4 [(LBT / ) - 1] GND Figure 3. MAX711 Adjustable Output oltage FB R1 R2 L1 C4 C2 9

10 Table 2. Component Selection INDUCTORS (L1) Sumida CD (1.5A), CDRH (1.23A), or CD Coilcraft DO33-08P µF, 16 tantalum capacitor Sprague 595D475X0016A2T where LBT is the desired threshold of the low-battery detector and is the voltage applied to the inverting input of the low-battery comparator. Since LBI current is less than 50nA, R3 and R4 can be large (typically 100kΩ to 1MΩ), minimizing input supply loading. If the low-battery comparator is not used, connect to and to, leaving unconnected. Inductor Selection A 22µH inductor value performs well in most applications. The inductance value is not critical, however, since the work with inductors in the 18µH to 100µH range. Smaller inductance values typically offer a smaller size for a given series resistance, allowing the smallest overall circuit dimensions. Circuits using larger inductance values exhibit higher output current capability and larger physical dimensions for a given series resistance. The inductor s incremental saturation current rating should be greater than the peak switch-current limit, which is 1.5A for = GND and 0.8A for =. However, it is generally acceptable to bias most inductors into saturation by as much as 20%, although this slightly reduces efficiency. The inductor s DC resistance significantly affects efficiency. See Tables 2 and 3 for a list of suggested inductors and suppliers. Capacitor Selection A 100µF, 16, 0.1Ω equivalent series resistance (ESR), surface-mount tantalum (SMT) output filter capacitor, C2, typically exhibits 50m output ripple when stepping up from 2 to 5 at 100mA. Smaller capacitors (down to 10µF with higher ESRs) are acceptable for light loads or in applications that can tolerate higher output ripple. The ESR of both bypass and filter capacitors affects efficiency and output ripple. Output voltage ripple is the product of the peak inductor current and the output capacitor s ESR. Use low-esr capacitors for best performance, or connect two or more filter capacitors in parallel. Low-ESR, SMT capacitors are currently available from Sprague (595D series) and AX (T series). Sanyo OS-CON organic-semiconductor through-hole capacitors also exhibit very low ESR and are especially CAPACITORS 100µF, 16 low-esr tantalum capacitor AX TE107M016R0100 or Sprague 593D107X0016E2W RECTIFIERS (D1) Schottky diode Motorola MBRS130T3 useful for operation at cold temperatures. The output capacitor, C3, needs to be only 4.7µF to maintain linear regulator stability. See Tables 2 and 3 for a list of suggested capacitors and suppliers. Rectifier Diode For optimum performance, use a switching Schottky diode. Refer to Tables 2 and 3 for the suggested diode and supplier. Applications Information The high-frequency operation makes PC layout important for minimizing ground bounce and noise. Keep the IC s GND pin and the ground leads of C1 and C2 (Figure 1) less than 0.2in. (5mm) apart. Also keep all connections to the FB and pins as short as possible. To maximize output power and efficiency and minimize output ripple voltage, use a ground plane and solder the IC s GND pin directly to the ground plane. Table 3. Component Suppliers SUPPLIER AX Coilcraft Motorola Sanyo Sprague Sumida PHONE (803) (847) (602) (619) (603) (847) FAX (803) (847) (602) (619) (603) (847) Chip Information TRANSISTOR COUNT: 661 SUBSTRATE CONNECTED TO GND 10

11 Package Information SOICN.E 11

12 NOTES 12

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