LT3467/LT3467A 1.1A Step-Up DC/DC Converter with Integrated Soft-Start DESCRIPTION FEATURES APPLICATIONS TYPICAL APPLICATION

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1 FEATURES n.3mhz Switching Frequency () n 2.MHz Switching Frequency (A) n Low V CESAT Switch: 33mV at.a n High Output Voltage: Up to 4V n Wide Input Range: 2.4V to 6V n Dedicated Soft-Start Pin n 5V at 54mA from 3.3V Input () n 5V at 43mA from 3.3V Input (A) n 2V at 27mA from 5V Input () n 2V at 26mA from 5V Input (A) n Uses Small Surface Mount Components n Low Shutdown Current: <μa n Pin-for-Pin Compatible with the LT93 and LT63 n Low Profi le (mm) ThinSOT Package n Low Profi le (.75mm) 8-Lead (3mm 2mm) DFN Package APPLICATIONS n Digital Cameras n White LED Power Supplies n Cellular Phones n Medical Diagnostic Equipment n Local 5V or 2V Supplies n TFT-LCD Bias Supplies n xdsl Power Supplies /A.A Step-Up DC/DC Converter with Integrated Soft-Start DESCRIPTION The LT 3467/A switching regulators combine a 42V,.A switch with a soft-start function. Pin compatible with the LT93, its low V CESAT bipolar switch enables the device to deliver high current outputs in a small footprint. The switches at.3mhz, allowing the use of tiny, low cost and low height inductors and capacitors. The A switches at 2.MHz, allowing the use of even smaller components. High inrush current at start-up is eliminated using the programmable soft-start function. A single external capacitor sets the current ramp rate. A constant frequency current mode PWM architecture results in low, predictable output noise that is easy to filter. The high voltage switch on the /A is rated at 42V, making the devices ideal for boost converters up to 4V as well as SEPIC and flyback designs. The can generate 5V at up to 54mA from a 3.3V supply or 5V at 45mA from four alkaline cells in a SEPIC design. The A can generate 5V at up to 43mA from a 3.3V supply or 5V at 35mA from a 3.3V supply. The / A are available in a low profile (mm) 6-lead SOT-23 package and tiny 3mm 2mm DFN package. L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. ThinSOT is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. TYPICAL APPLICATION Effi ciency 2.6V TO 4.2V 4.7μF OFF ON Single Li-Ion Cell to 5V Boost Converter 2.7μH SW 42k 3.3pF 5V 765mA AT = 4.2V, 54mA AT = 3.3V, 36mA AT = 2.6V EFFICIENCY (%) = 3.3V = 2.6V = 4.2V.47μF 33k 5μF TAa I OUT (ma) 3467 TAb

2 /A ABSOLUTE MAXIMUM RATINGS Voltage...6V SW Voltage....4V to 42V Voltage...2.5V Current Into Pin... ±ma Voltage... 6V Maximum Junction Temperature C (Note ) Operating Junction Temperature Range (Note 2) E Grade... 4 C to 85 C I Grade... 4 C to 25 C Storage Temperature Range C to 5 C Lead Temperature (Soldering, sec) TSOT... 3 C PIN CONFIGURATION TOP VIEW SW SW SW 2 3 TOP VIEW DDB PACKAGE 8-LEAD (3mm 2mm) PLASTIC DFN T JMAX = 25 C, θ JA = 8 C/W EXPOSED PAD (PIN 9) IS, MUST BE SOLDERED TO PCB S6 PACKAGE 6-LEAD PLASTIC TSOT-23 T JMAX = 25 C, θ JA = 65 C/W, θ JC = 2 C/W ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE EDDB#PBF EDDB#TRPBF LCPX 8-Lead (3mm 2mm) Plastic DFN 4 C to 85 C IDDB#PBF IDDB#TRPBF LCPX 8-Lead (3mm 2mm) Plastic DFN 4 C to 25 C AEDDB#PBF AEDDB#TRPBF LCKD 8-Lead (3mm 2mm) Plastic DFN 4 C to 85 C AIDDB#PBF AIDDB#TRPBF LCKD 8-Lead (3mm 2mm) Plastic DFN 4 C to 25 C IS6#PBF IS6#TRPBF LTACH 6-Lead Plastic TSOT-23 4 C to 25 C ES6#PBF ES6#TRPBF LTACH 6-Lead Plastic TSOT-23 4 C to 85 C AES6#PBF AES6#TRPBF LTBCC 6-Lead Plastic TSOT-23 4 C to 85 C AIS6#PBF AIS6#TRPBF LTBCC 6-Lead Plastic TSOT-23 4 C to 25 C LEAD BASED FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE EDDB EDDB#TR LCPX 8-Lead (3mm 2mm) Plastic DFN 4 C to 85 C IDDB IDDB#TR LCPX 8-Lead (3mm 2mm) Plastic DFN 4 C to 25 C AEDDB AEDDB#TR LCKD 8-Lead (3mm 2mm) Plastic DFN 4 C to 85 C AIDDB AIDDB#TR LCKD 8-Lead (3mm 2mm) Plastic DFN 4 C to 25 C IS6 IS6#TR LTACH 6-Lead Plastic TSOT-23 4 C to 25 C ES6 ES6#TR LTACH 6-Lead Plastic TSOT-23 4 C to 85 C AES67 AES6#TR LTBCC 6-Lead Plastic TSOT-23 4 C to 85 C AIS67 AIS67#TR LTBCC 6-Lead Plastic TSOT-23 4 C to 25 C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: For more information on tape and reel specifi cations, go to: 2

3 ELECTRICAL CHARACTERISTICS /A The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at T A = 25 C. = 3V, V = unless otherwise noted. Specifi cations are for both the and A unless otherwise noted. PARAMETER CONDITIONS MIN TYP MAX UNITS Minimum Operating Voltage V Maximum Operating Voltage 6 V Feedback Voltage V l V Pin Bias Current (Note 3) l 5 na Quiescent Current V = 2.4V, Not Switching.2 2 ma Quiescent Current in Shutdown V =.5V, = 3V. μa Reference Line Regulation 2.6V 6V..5 %/V Switching Frequency A MHz MHz A l.6 MHz Maximum Duty Cycle % l 87 % A % A l 78 % Minimum Duty Cycle % Switch Current Limit At Minimum Duty Cycle At Maximum Duty Cycle (Note 4) A A Switch V CESAT I SW =.A 33 5 mv Switch Leakage Current V SW = 5V. μa Input Voltage High 2.4 V Input Voltage Low.5 V Pin Bias Current V = 3V V = V Charging Current V =.5V μa μa μa Note : Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The E/AE are guaranteed to meet performance specifications from C to 85 C, junction temperature. Specifi cations over the 4 C to 85 C operating junction temperature range are assured by design, characterization and correlation with statistical process controls. The I/AI are guaranteed over the full 4 C to 25 C operating junction temperature range. Note 3: Current fl ows out of the pin. Note 4: See Typical Performance Characteristics for guaranteed current limit vs duty cycle. 3

4 /A TYPICAL PERFORMANCE CHARACTERISTICS I Q (ma) Quiescent Current vs Temperature Pin Voltage vs Temperature Current vs Voltage V (V) I (μa) 4 T A = 25 C TEMPERATURE ( C) TEMPERATURE ( C) V (V) 3467 G 3467 G G3 I LIM (A) Current Limit vs Duty Cycle GUARANTEED TYPICAL T A = 25 C DC (%) V CESAT mv/div Switch Saturation Voltage vs Switch Current T A = 85 C SW CURRENT 2mA/DIV T A = 25 C T A = 4 C 3467 G5 OSCILLATOR FREQUENCY (MHz) Oscillator Frequency vs Temperature TEMPERATURE ( C) A 3467 G G6 I (μa) Soft-Start Current vs Soft-Start Voltage T A = 25 C SWITCH CURRENT (A) Peak Switch Current vs Soft-Start Voltage T A = 25 C V 2V/DIV V/DIV Start-Up Waveform (Figure 2 Circuit).4.2 I SUPPLY.5A/DIV V (mv) V (mv).5ms/div 3467 G G G8 4

5 /A PIN FUNCTIONS (DFN/TSOT) (Pin /Pin 3): Feedback Pin. Reference voltage is.255v. Connect resistive divider tap here. Minimize trace area at. Set =.255V( + /). (Pins 2, 5, 9/Pin 2): Ground. Tie directly to local ground plane. SW (Pins 3, 4/Pin ): Switch Pin. (Collector of internal NPN power switch) Connect inductor/diode here and minimize the metal trace area connected to this pin to minimize EMI. (Pin 6/Pin 6): Input Supply Pin. Must be locally bypassed. (Pin 7/Pin 5): Soft-Start Pin. Place a soft-start capacitor here. Upon start-up, 4μA of current charges the capacitor to.255v. Use a larger capacitor for slower start-up. Leave floating if not in use. (Pin 8/Pin 4): Shutdown Pin. Tie to 2.4V or more to enable device. Ground to shut down. BLOCK DIAGRAM 25k (EXTERNAL) (EXTERNAL).255V REFERENCE + A R C C C RAMP GENERATOR + COMPARATOR A2 R S Q DRIVER + Q SW.Ω SHUTDOWN.3MHz OSCILLATOR* *2.MHz FOR A 3467 F Figure. Block Diagram 5

6 /A OPERATION The uses a constant frequency, current-mode control scheme to provide excellent line and load regulation. Refer to the Block Diagram. At the start of each oscillator cycle, the SR latch is set which turns on the power switch Q. A voltage proportional to the switch current is added to a stabilizing ramp and the resulting sum is fed into the positive terminal of the PWM comparator A2. When this voltage exceeds the level at the negative input of A2, the SR latch is reset, turning off the power switch. The level at the negative input of A2 is set by the error amplifier A, and is simply an amplified version of the difference between the feedback voltage and the reference voltage of.255v. In this manner, the error amplifi er sets the correct peak current level to keep the output in regulation. If the error amplifi er s output increases, more current is delivered to the output. Similarly, if the error decreases, less current is delivered. The soft-start feature of the allows for clean start-up conditions by limiting the rate of voltage rise at the output of comparator A which, in turn, limits the peak switch current. The soft-start pin is connected to a reference voltage of.255v through a 25k resistor, providing 4μA of current to charge the soft-start capacitor. Typical values for the soft-start capacitor range from nf to 2nF. The has a current limit circuit not shown in the Block Diagram. The switch current is constantly monitored and not allowed to exceed the maximum switch current (typically.4a). If the switch current reaches this value, the SR latch is reset regardless of the state of comparator A2. This current limit protects the power switch as well as the external components connected to the. The Block Diagram for the A (not shown) is identical except that the oscillator frequency is 2.MHz. APPLICATIONS INFORMATION Duty Cycle The typical maximum duty cycle of the is 94% (88% for the A). The duty cycle for a given application is given by: DC = + V D + V D V CESAT where V D is the diode forward voltage drop and V CESAT is in the worst case 33mV (at.a) The and A can be used at higher duty cycles, but must be operated in the discontinuous conduction mode so that the actual duty cycle is reduced. Setting Output Voltage and determine the output voltage. =.255V (+ /) Switching Frequency and Inductor Selection The switches at.3 MHz, allowing for small valued inductors to be used. 4.7μH or μh will usually suffi ce. The A switches at 2.MHz, allowing for even smaller valued inductors to be used..9μh to 6.8μH will usually suffice. Choose an inductor that can handle at least.2a without saturating, and ensure that the inductor has a low DCR (copper-wire resistance) to minimize I 2 R power losses. Note that in some applications, the current handling requirements of the inductor can be lower, such as in the SEPIC topology where each inductor only carries one-half of the total switch current. For better efficiency, use similar valued inductors with a larger volume. Many different sizes and shapes are available from various manufacturers. Choose a core material that has low losses at.3mhz, (2.MHz for the A) such as ferrite core. 6

7 APPLICATIONS INFORMATION /A 2.6V TO 4.2V 4.7μF OFF ON.47μF 2.7μH SW 42k 33k C4 3.3pF 5V 765mA AT = 4.2V, 54mA AT = 3.3V, 36mA AT = 2.6V 5μF, : X5R OR X7R, 6.3V : ON SEMICONDUCTOR MBRM2 : SUMIDA CR43-2R TA5a Figure 2. Single Li-Ion Cell to 5V Boost Converter (Same as st Page Application) Table. Inductor Manufacturers Sumida (847) TDK (847) Murata (74) FDK (48) Soft-Start The soft-start feature provides a way to limit the inrush current drawn from the supply upon start-up. An internal 25k resistor charges the external soft-start capacitor to.255v. After the capacitor reaches.5v the rate of voltage rise at the output of the comparator A tracks the rate of voltage rise of the soft-start capacitor. This limits the inrush current drawn from the supply during startup. The soft-start feature plays another important role in applications where the switch will reach levels of 3V or higher. During start-up, excessively high switch current, together with the presence of high voltage can overstress the switch. A properly used soft-start feature will keep the switch current from overshooting. This practice will greatly improve the robustness of such designs. Once the part is shut down, the soft-start capacitor is quickly discharged to.4v, then slowly discharged through the 25k resistor to ground. If the part is to be shut down and re-enabled in a short period of time while soft-start is used, you must ensure that the soft-start capacitor has enough time to discharge before re-enabling the part. Typical values of the soft-start capacitor range from nf to 2nF. V/DIV I SUPPLY.5A/DIV V/DIV I SUPPLY.5A/DIV Supply Current of Figure 2 During Start-Up Without Soft-Start Capacitor.ms/DIV 3467 AI Supply Current of Figure 2 During Start-Up with a 47nF Soft-Start Capacitor.5ms/DIV 3467 AI2 7

8 /A APPLICATIONS INFORMATION Capacitor Selection Low ESR (equivalent series resistance) capacitors should be used at the output to minimize the output ripple voltage. Multi-layer ceramic capacitors are an excellent choice, as they have extremely low ESR and are available in very small packages. X5R dielectrics are preferred, followed by X7R, as these materials retain the capacitance over wide voltage and temperature ranges. A 4.7μF to 5μF output capacitor is sufficient for most applications, but systems with very low output currents may need only a μf or 2.2μF output capacitor. Solid tantalum or OS-CON capacitors can be used, but they will occupy more board area than a ceramic and will have a higher ESR. Always use a capacitor with a suffi cient voltage rating. Ceramic capacitors also make a good choice for the input decoupling capacitor, which should be placed as close as possible to the. A μf to 4.7μF input capacitor is sufficient for most applications. Table 2 shows a list of several ceramic capacitor manufacturers. Consult the manufacturers for detailed information on their entire selection of ceramic parts. Table 2. Ceramic Capacitor Manufacturers Taiyo Yuden (48) AVX (83) Murata (74) The decision to use either low ESR (ceramic) capacitors or the higher ESR (tantalum or OS-CON) capacitors can affect the stability of the overall system. The ESR of any capacitor, along with the capacitance itself, contributes a zero to the system. For the tantalum and OS-CON capacitors, this zero is located at a lower frequency due to the higher value of the ESR, while the zero of a ceramic capacitor is at a much higher frequency and can generally be ignored. A phase lead zero can be intentionally introduced by placing a capacitor (C4) in parallel with the resistor () between and V as shown in Figure 2. The frequency of the zero is determined by the following equation. ƒ Z = 2π C4 By choosing the appropriate values for the resistor and capacitor, the zero frequency can be designed to improve the phase margin of the overall converter. The typical target value for the zero frequency is between 35kHz to 55kHz. Figure 3 shows the transient response of the step-up converter from Figure 8 without the phase lead capacitor C4. Although adequate for many applications, phase margin is not ideal as evidenced by 2-3 bumps in both the output voltage and inductor current. A 22pF capacitor for C4 results in ideal phase margin, which is revealed in Figure 4 as a more damped response and less overshoot. Diode Selection A Schottky diode is recommended for use with the and the A. The Philips PMEG 25 is a very good choice. Where the switch voltage exceeds 2V, use the PMEG 35 (a 3V diode). Where the switch voltage exceeds 3V, use the PMEG 45 (a 4V diode). These diodes are rated to handle an average forward current of.5a. In applications where the average forward current of the diode exceeds.5a, a Philips PMEG 2 rated at A is recommended. For higher efficiency, use a diode with better thermal characteristics such as the On Semiconductor MBRM2 (a 2V diode) or the MBRM4 (a 4V diode). 8

9 APPLICATIONS INFORMATION LOAD CURRENT ma/div AC COUPLED 2mV/DIV AC COUPLED I 5A/DIV AC COUPLED 2μs/DIV 3467 F3 /A Layout Hints The high speed operation of the /A demands careful attention to board layout. You will not get advertised performance with careless layout. Figure 5a shows the recommended component placement for the ThinSOT package. Figure 5b shows the recommended component placement for the DFN package. Note the vias under the Exposed Pad. These should connect to a local ground plane for better thermal performance. Figure 3. Transient Response of Figure 8 s Step-Up Converter without Phase Lead Capacitor LOAD CURRENT ma/div AC COUPLED C 2mV/DIV AC COUPLED 3 4 I 5A/DIV AC COUPLED 3467 F5a 2μs/DIV 3467 F4 Figure 4. Transient Response of Figure 8 s Step-Up Converter with a 22pF Phase Lead Capacitor Figure 5a. Suggested Layout ThinSOT Setting Output Voltage To set the output voltage, select the values of and (see Figure 2) according to the following equation. =.255V A good value for is 3.3k which sets the current in the resistor divider chain to.255v/3.3k = 94μA C 3467 F5b Figure 5b. Suggested Layout DFN 9

10 /A APPLICATIONS INFORMATION Compensation Theory Like all other current mode switching regulators, the /A needs to be compensated for stable and efficient operation. Two feedback loops are used in the /A: a fast current loop which does not require compensation, and a slower voltage loop which does. Standard Bode plot analysis can be used to understand and adjust the voltage feedback loop. As with any feedback loop, identifying the gain and phase contribution of the various elements in the loop is critical. Figure 6 shows the key equivalent elements of a boost converter. Because of the fast current control loop, the power stage of the IC, inductor and diode have been replaced by the equivalent transconductance amplifi er g mp. g mp acts as a current source where the output current is proportional to the V C voltage. Note that the maximum output current of gmp is fi nite due to the current limit in the IC. V C R C C C R O + g mp g ma + C PL.255V REFERENCE C C : COMPENSATION CAPACITOR C OUT : OUTPUT CAPACITOR C PL : PHASE LEAD CAPACITOR g ma : TRANSCONDUCTANCE AMPLIFIER INSIDE IC g mp : POWER STAGE TRANSCONDUCTANCE AMPLIFIER R C : COMPENSATION RESISTOR R L : OUTPUT RESISTANCE DEFINED AS DIVIDED BY I LOAD(MAX) R O : OUTPUT RESISTANCE OF g ma, : FEEDBACK RESISTOR DIVIDER NETWORK R ESR : OUTPUT CAPACITOR ESR 3467 F6 R ESR C OUT R L From Figure 6, the DC gain, poles and zeroes can be calculated as follows: 2 Output Pole: P= 2 π R L C OUT Error Amp Pole: P2= 2 π R O C C Error Amp Zero: Z= 2 π R C C C DC GAIN: A= V g ma R O g mp R L OUT 2 ESR Zero: Z2 = 2 π R ESR C OUT V 2 RHP Zero: Z3= IN R L 2 π V 2 OUT L High Frequency Pole: P3> f S 3 Phase Lead Zero: Z4 = 2 π C PL Phase Lead Pole: P4 = 2 π C PL + The current mode zero is a right-half plane zero which can be an issue in feedback control design, but is manageable with proper external component selection. Figure 6. Boost Converter Equivalent Model

11 APPLICATIONS INFORMATION Using the circuit of Figure 2 as an example, the following table shows the parameters used to generate the Bode plot shown in Figure 7. GAIN (db) GAIN 45 PHASE 5 45 k k k M FREQUENCY (Hz) 3467 F7 Figure 7. Bode Plot of 3.3V to 5V Application PHASE (DEG) /A Table 3. Bode Plot Parameters PARAMETER VALUE UNITS COMMENT R L.4 Ω Application Specific C OUT 5 μf Application Specific R ESR mω Application Specific R O.4 MΩ Not Adjustable C C 6 pf Not Adjustable C PL 3.3 pf Adjustable R C kω Not Adjustable 42 kω Adjustable 33 kω Adjustable 5 V Application Specific 3.3 V Application Specific g ma 35 μmho Not Adjustable g mp 7.5 mho Not Adjustable L 2.7 μh Application Specific f S.3* MHz Not Adjustable *2.MHz for A From Figure 7, the phase is 38 when the gain reaches db giving a phase margin of 42. This is more than adequate. The crossover frequency is 37kHz. TYPICAL APPLICATIONS Lithium-Ion to 6V Step-Up DC/DC Converter Li-Ion to 6V 2.7V TO 4.2V 2.2μF C4.47μF 2.2μH SW 5k 33k.8pF 6V 275mA AT = 2.7V 49mA AT = 3.8V 59mA AT = 4.2V 5μF EFFICIENCY (%) = 2.7V = 4.2V = 3.8V, : X5R OR X7R, 6.3V : ON SEMICONDUCTOR MBRM2 : SUMIDA CR TA I OUT (ma) 3467 TA2b

12 /A TYPICAL APPLICATIONS 4-Cell to 5V SEPIC Converter 4-CELL BATTERY 4V TO 6.5V 2.2μF C4.47μF μh SW μf 255k 84.5k C5 4.7pF L2 μh 5V 325mA AT = 4V 4mA AT = 5V 45mA AT = 6.5V μf, : X5R or X7R, V : X5R or X7R, 6.3V : PHILIPS PMEG 2, L2: MURATA LQH32CNK33L 3467 TA3 5V to 4V Boost Converter 5V 4.7μF 2.7μH SW 42k 4V 2mA μf.μf 3.3k : X5R or X7R, 6.3V : X5R or X7R, 5V : ON SEMICONDUCTOR, MBRM4 : SUMIDA CD43-2R TA4a ±5V Dual Output Converter with Output Disconnect 5V 2.2μF OFF ON SW μh C4 μf C5 μf R3 Ω D2 47k 5V ma 2.2μF C6.47μF 3.3k : X5R or X7R, 6.3V TO C5: X5R or X7R, 6V TO D4: PHILIPS PMEG 25 : SUMIDA CR43- D3 R4 Ω D4 2.2μF 3467 TA5 5V ma 2

13 TYPICAL APPLICATIONS 9V, 8V, 9V Triple Output TFT-LCD Bias Supply with Soft-Start /A 3.3V V 2.2μF 4.7μH SW D2.μF D5 C4 μf 24k 8V ma 9V 22mA C5 μf 9PUT 5V/DIV 9PUT 5V/DIV Start-Up Waveforms V 3.3V C7.μF.μF 2k 8PUT V/DIV : X5R OR X7R, 6.3V,, C5, C6: X5R OR X7R, V C4: X5R OR X7R, 25V TO D4: PHILIPS BAT54S OR EQUIVALENT D5: PHILIPS PMEG 25 : PANASONIC ELT5KT4R7M D4 D3 C6 μf 9V ma 3467 TA6a I.5A/DIV 2ms/DIV 3467 TA6b 8V, 23V, 8V Triple Output TFT-LCD Bias Supply with Soft-Start D2.μF D3 C4.μF D4 C5.μF 23V ma C6 μf Start-Up Waveforms V 3.3V V 3.3V 2.2μF C9.μF 4.7μH SW D7.μF 3k 2k 8V 27mA C7 μf 8PUT 5V/DIV 8PUT 5V/DIV 23PUT V/DIV : X5R OR X7R, 6.3V TO C4, C7, C8: X5R OR X7R, V C5: X5R OR X7R, 6V C6: X5R OR X7R, 25V TO D6: PHILIPS BAT54S OR EQUIVALENT D7: PHILIPS PMEG 25 : PANASONIC ELT5KT4R7M D5 D6 C8 μf 3467 TA7a 8V ma I.5A/DIV 2ms/DIV 3467 TA7b 3

14 /A TYPICAL APPLICATIONS Single Li-Ion Cell to 5V Boost Converter Effi ciency 2.6V TO 4.2V 4.7μF OFF ON.47μF.9μH SW A 8.6k 2.67k C4* 75pF 5V 6mA AT = 4.2V 36mA AT = 3.3V 25mA AT = 2.6V * 22μF EFFICIENCY (%) = 2.6V = 3.3V = 4.2V, : X5R OR X7R, 6.3V : PHILIPS PMEG 2 : FDK MIPW3226DR9M * CAN BE μf IN A 2 OR LARGER PACKAGE WITH THE ADDITION OF C4, OTHERWISE C4 IS OPTIONAL 3467 TA9a I OUT (ma) 3467 TA9b 2.6V-3.3V to 5V Boost Converter Effi ciency 2.6V TO 3.3V 4.7μF OFF ON.47μF, : X5R OR X7R, 6.3V : PHILIPS PMEG 2 : FDK MIP3226R5M.5μH SW A 8.6k 2.67k C4 56pF 5V 43mA AT = 3.3V 27mA AT = 2.6V μf 3467 TA8a EFFICIENCY (%) = 3.3V = 2.6V I OUT (ma) 3467 TA8b 3.3V to 5V, 35mA Step-Up Converter Effi ciency 3.3V 4.7μF OFF ON.47μF 6.8μH SW A 6.5k.5k C4 68pF 5V 35mA 2.2μF EFFICIENCY (%) : X5R OR X7R, 6.3V : X5R OR X7R, 6V : PHILIPS PMEG 2 : SUMIDA CMD43-6R8MC 3467 TAa I OUT (ma) 3467 TAb 4

15 PACKAGE DESCRIPTION DDB Package 8-Lead Plastic DFN (3mm 2mm) (Reference LTC DWG # Rev B) /A (2 SIDES).7.5 PACKAGE OUTLINE BSC (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS PIN BAR TOP MARK (SEE NOTE 6).2 REF 3.. (2 SIDES) 2.. (2 SIDES) R =.5 TYP.56.5 (2 SIDES) R =.5 TYP (2 SIDES) BOTTOM VIEW EXPOSED PAD BSC PIN R =.2 OR CHAMFER (DDB8) DFN 95 REV B NOTE:. DRAWING CONFORMS TO VERSION (WECD-) IN JEDEC PACKAGE OUTLINE M DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED.5mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN LOCATION ON THE TOP AND BOTTOM OF PACKAGE 5

16 /A PACKAGE DESCRIPTION S6 Package 6-Lead Plastic TSOT-23 (Reference LTC DWG # ).62 MAX.95 REF 2.9 BSC (NOTE 4).22 REF 3.85 MAX 2.62 REF.4 MIN 2.8 BSC.5.75 (NOTE 4) PIN ONE ID RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR.95 BSC PLCS (NOTE 3) BSC DATUM A. MAX REF BSC (NOTE 3) S6 TSOT-23 5 NOTE:. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED.254mm 6. JEDEC PACKAGE REFERENCE IS MO-93 6

17 /A REVISION HISTORY (Revision history begins at Rev E) REV DATE DESCRIPTION PAGE NUMBER E 4/ Updated Note 2 in Absolute Maximum Ratings and Electrical Characteristics 2, 3 Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 7

18 /A TYPICAL APPLICATIONS 5V 2.2μF.47μF 4.7μH SW 5k 3.3k C4* 22pF 2V 27mA μf EFFICIENCY (%) Effi ciency : X5R OR X7R, 6.3V : X5R OR X7R, 6V : PHILIPS PMEG 2 : SUMIDA CR43-4R7 *OPTIONAL 3467 F8a Figure 8. 5V to 2V, 27mA Step-Up Converter I OUT (ma) 3467 F8b 5V 4.7μF OFF ON.47μF 3.3μH SW A : X5R OR X7R, 6.3V : X5R OR X7R, 6V : PHILIPS PMEG 2 : SUMIDA CDRH48-3R3 5k 3.3k C4 2pF 2V 26mA μf 3467 F9a Figure 9. 5V to 2V, 26mA Step-Up Converter EFFICIENCY (%) Effi ciency I OUT (ma) 3467 F9b RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT65/LT65-3mA/8mA (I SW ), High Effi ciency Step-Up DC/DC Converter : V to 5V, (MAX) = 34V, I Q = 2μA, I SD < μa, ThinSOT Package LT68.5A (I SW ),.25MHz, High Effi ciency Step-Up DC/DC Converter 9% Effi ciency, :.6V to 8V, (MAX) = 35V, I Q =.8mA, I SD < μa, MS Package LT7 No R SENSE, 53kHz, Synchronous Step-Up DC/DC Controller 95% Effi ciency, :.9V to 5V, I Q = 2μA, I SD < μa, MS Package LT87 Wide Input Range, MHz, No R SENSE Current Mode Boost, Flyback and SEPIC Controller 92% Effi ciency, : 2.5V to 36V, I Q = 25μA, I SD < μa, MS Package LT93/LT93A A (I SW ),.2MHz/2.2MHz, High Effi ciency Step-Up DC/DC Converter High Effi ciency, : 2.6V to 6V, (MAX) = 34V, I Q = 4.2mA/5.5mA, I SD < μa, ThinSOT Package LT946/LT946A.5A (I SW ),.2MHz/2.7MHz, High Effi ciency Step-Up DC/DC Converter with Soft-Start High Effi ciency, : 2.45V to 6V, (MAX) = 34V, I Q = 3.2mA, I SD < μa, MS8 Package LT96.5A (I SW ),.25MHz, High Effi ciency Step-Up DC/DC Converter 9% Effi ciency, : 3V to 25V, (MAX) = 35V, I Q =.9mA, I SD < 6μA, MS8E Package LT4/ LT4B 6mA (I SW ),.2MHz, Synchronous Step-Up DC/DC Converter 92% Effi ciency, :.85V to 5V, (MAX) = 5V, I Q = 9μA/3μA, I SD < μa, ThinSOT Package LT4 A (I SW ), 3MHz, Synchronous Step-Up DC/DC Converter 97% Effi ciency, :.5V to 5V, (MAX) = 5.5V, I Q = 38μA, I SD < μa, MS Package LT42 2A (I SW ), 3MHz, Synchronous Step-Up DC/DC Converter 97% Effi ciency, :.5V to 5V, (MAX) = 5.5V, I Q = 38μA, I SD < μa, MS Package LT mA (I SW ), High Effi ciency Step-Up DC/DC Converter with Integrated Schottky and PNP Disconnect : 2.3V to V, (MAX) = 34V, I Q = 25μA, I SD < μa, ThinSOT Package No R SENSE is a trademark of Linear Technology Corporation. 8 LT 4 REV E PRINTED IN USA Linear Technology Corporation 63 McCarthy Blvd., Milpitas, CA (48) FAX: (48) LINEAR TECHNOLOGY CORPORATION 23

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