FEATURES TYPICAL APPLICATIO. LT1931/LT1931A 1.2MHz/2.2MHz Inverting DC/DC Converters in ThinSOT DESCRIPTIO APPLICATIO S

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1 FEATRES Fixed Frequency.2MHz/2.2MHz Operation Very Low Noise: mv P-P Output Ripple at 35mA from Input 2V at 5mA from Input ses Small Surface Mount Components Wide Input Range: 2.6V to 6V Low Shutdown Current: <µa Low V CESAT Switch: 4mV at A Pin-for-Pin Compatible with the LT6 Low Profile (mm) ThinSOT TM Package APPLICATIO S Disk Drive MR Head Bias Digital Camera CCD Bias LCD Bias GaAs FET Bias Local Low Noise/Low Impedance Negative Supply /A.2MHz/2.2MHz Inverting DC/DC Converters in ThinSOT DESCRIPTIO The LT 93/A are the industry s highest power inverting SOT-23 current mode DC/DC converters. Both parts include a A integrated switch allowing high current outputs to be generated in a small footprint. The switches at.2mhz while the A switches at 2.2MHz. These high speeds enable the use of tiny, low cost capacitors and inductors 2mm or less in height. The is capable of generating at 35mA or 2V at 5mA from a supply, while the A can generate at 3mA using significantly smaller inductors. Both parts are easy pin-for-pin upgrades for higher power LT6 applications. The /A operate in a dual inductor inverting topology that filters both the input side and output side current. Very low output voltage ripple approaching mv P-P can be achieved when ceramic output capacitors are used. Fixed frequency switching ensures a clean output free from low frequency noise typically present with charge pump solutions. The low impedance output remains within % of nominal during large load steps. The 36V switch allows to differential of up to 34V. The /A are available in the 5-lead ThinSOT package., LTC and LT are registered trademarks of Linear Technology Corporation. ThinSOT is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. TYPICAL APPLICATIO LA SW 29.4k k 22pF LB 35mA 22µF EFFICIENCY (%) Efficiency : TAIYO YDEN X5R JMK22BJ475MG : TAIYO YDEN X5R LMK22BJ5MG : TAIYO YDEN X5R JMK325BJ226MM : ON SEMICONDCTOR MBR52 L: SMIDA CLS62- Figure. to, 35mA Inverting DC/DC Converter 93 F LOAD CRRENT (ma) 93 TA

2 /A ABSOLTE AXI RATI GS W W W (Note ) Voltage... 6V SW Voltage....4V to 36V Voltage... 2V Current Into Pin... ±ma Voltage... 6V Maximum Junction Temperature C Operating Temperature Range (Note 2).. 4 C to 85 C Storage Temperature Range C to 5 C Lead Temperature (Soldering, sec)... 3 C W PACKAGE/ORDER I FOR ATIO SW 2 3 ORDER PART NMBER ES5 AES5 IS5 AIS5 TOP VIEW 5 4 S5 PACKAGE 5-LEAD PLASTIC TSOT-23 T JMAX = 25 C, θ JA = 5 C/ W S5 PART MARKING LTRA LTSP LTBZF LTBZG Order Options Tape and Reel: Add #TR Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF Lead Free Part Marking: Consult LTC Marketing for parts specified with wider operating temperature ranges. ELECTRICAL CHARACTERISTICS The denotes specifications which apply over the full operating temperature range, otherwise specifications are T A = 25 C. = 3V, V =, unless otherwise noted. (Note 2) A PARAMETER CONDITIONS MIN TYP MAX MIN TYP MAX NITS Minimum Operating Voltage V Maximum Operating Voltage 6 6 V Feedback Voltage V V Pin Bias Current V = µa Quiescent Current V = 2.4V, Not Switching ma Quiescent Current in Shutdown V = V, = 3V.. µa Reference Line Regulation 2.6V 6V %/V Switching Frequency MHz MHz Maximum Duty Cycle % Switch Current Limit (Note 3) A Switch V CESAT I SW = A mv Switch Leakage Current V SW =.. µa Input Voltage, High V Input Voltage, Low.5.5 V Pin Bias Current V = 3V µa V = V.. µa Note : Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: The E/AE are guaranteed to meet performance specifications from C to 7 C. Specifications over the 4 C to 85 C 2 operating temperature range are assured by design, characterization and correlation with statistical process controls. I/AI are guaranteed over the 4 C to 85 C temperature range. Note 3: Current limit guaranteed by design and/or correlation to static test.

3 /A TYPICAL PERFOR A CE CHARACTERISTICS W QIESCENT CRRENT (ma) Quiescent Current 7. NOT SWITCHING A TEMPERATRE ( C) FEEDBACK VOLTAGE (V) Feedback Pin Voltage TEMPERATRE ( C) 75 PIN CRRENT (µa) Shutdown Pin Current 9 T A = 25 C 8 A PIN VOLTAGE (V) 6 93 G 93 G2 93 G3 CRRENT LIMIT (A) Current Limit Switch Saturation Voltage Oscillator Frequency DTY CYCLE (%) T A = 25 C 9 V CESAT (V) T A = 25 C SWITCH CRRENT (A) FREQENCY (MHz) A TEMPERATRE ( C) G4 93 G5 93 G6 PI F CTIO S SW (Pin ): Switch Pin. Connect inductor/diode here. Minimize trace area at this pin to keep EMI down. (Pin 2): Ground. Tie directly to local ground plane. (Pin 3): Feedback Pin. Reference voltage is.25. Connect resistive divider tap here. Minimize trace area. The bias current flows out of the pin. Set and according to: VOT. 255 For A: = ( ) (Pin 4): Shutdown Pin. Tie to 2.4V or more to enable device. Ground to shut down. (Pin 5): Input Supply Pin. Must be locally bypassed. For : = VOT ( ) 3

4 /A BLOCK DIAGRA W 5 C PL (OPTIONAL) Q (EXTERNAL) (EXTERNAL) R5 8k R6 8k Q2 x 3 R3 3k R4 5k + A g m R C C C RAMP GENERATOR.2MHz OSCILLATOR Σ 4 + COMPARATOR A2 SHTDOWN R LATCH S Q DRIVER + SW Q3.Ω 2 93 BD Figure 2 OPERATIO The uses a constant frequency, current mode control scheme to provide excellent line and load regulation. Operation can be best understood by referring to the Block Diagram in Figure 2. At the start of each oscillator cycle, the SR latch is set, turning on the power switch Q3. A voltage proportional to the switch current is added to a stabilizing ramp and the resulting sum is fed into the positive terminal of the PWM comparator A2. When this voltage exceeds the level at the negative input of A2, the SR latch is reset, turning off the power switch. The level at the negative input of A2 is set by the error amplifier (g m ) and is simply an amplified version of the difference between the feedback voltage and the reference voltage of.25. In this manner, the error amplifier sets the correct peak current level to keep the output in regulation. If the error amplifier s output increases, more current is taken from the output; if it decreases, less current is taken. One function not shown in Figure 2 is the current limit. The switch current is constantly monitored and not allowed to exceed the nominal value of.2a. If the switch current reaches.2a, the SR latch is reset regardless of the state of comparator A2. This current limit protects the power switch as well as various external components connected to the. The Block Diagram for the A is identical except that the oscillator is 2.2MHz and resistors R3 to R6 are one-half the values. 4

5 APPLICATIO S I FOR ATIO W A AND DIFFERENCES: Switching Frequency The key difference between the A and is the faster switching frequency of the A. At 2.2MHz, the A switches at nearly twice the rate of the. Care must be taken in deciding which part to use. The high switching frequency of the A allows smaller cheaper inductors and capacitors to be used in a given application, but with a slight decrease in efficiency and maximum output current when compared to the. Generally, if efficiency and maximum output current are critical, the should be used. If application size and cost are more important, the A will be the better choice. In many applications, tiny inexpensive chip inductors can be used with the A, reducing solution cost. Duty Cycle The maximum duty cycle (DC) of the A is 75% compared to 84% for the. The duty cycle for a given application using the dual inductor inverting topology is given by: VOT DC = V + V IN OT For a to application, the DC is 5% indicating that the A can be used. A to 6V application has a DC of 76.2% making the the right choice. The A can still be used in applications where the DC, as calculated above, is above 75%. However, the part must be operated in the discontinuous conduction mode so that the actual duty cycle is reduced. INDCTOR SELECTION Several inductors that work well with the are listed in Table and those for the A are listed in Table 2. Besides these, there are many other inductors that can be used. Consult each manufacturer for detailed information and for their entire selection of related parts. Ferrite core inductors should be used to obtain the best efficiency, as /A core losses at frequencies above MHz are much lower for ferrite cores than for powdered-iron units. When using coupled inductors, choose one that can handle at least A of current without saturating, and ensure that the inductor has a low DCR (copper-wire resistance) to minimize I 2 R power losses. If using uncoupled inductors, each inductor need only handle one-half of the total switch current so that.5a per inductor is sufficient. A 4.7µH to 5µH coupled inductor or a 5µH to 22µH uncoupled inductor will usually be the best choice for most designs. For the A, a 2.2µH to 4.7µH coupled inductor or a 3.3µH to uncoupled inductor will usually suffice. In certain applications such as the Charge Pump inverting DC/DC converter, only a single inductor is used. In this case, the inductor must carry the entire A switch current. Table. Recommended Inductors L Size PART (µh) (L W H) mm VENDOR CLS Sumida CR (847) CR CTX Coiltronics CTX5-5 (47) www. coiltronics.com LQH3K Murata LQH45K4 5 (44) Table 2. Recommended Inductors A L Size PART (µh) (L W H) mm VENDOR ELJPR3MF Panasonic ELJPR7MF 4.7 (48) CLQ4-4R Sumida CLQ4-6R (847) LB264R7M Taiyo Yuden LB263R3M 3.3 (48) LQH3R7K Murata LQH4K24 (44) se drawing #5382-T39 2 se drawing #5382-T4 5

6 /A APPLICATIO S I FOR ATIO W The inductors shown in Table 2 for use with the A were chosen for their small size. For better efficiency, use similar valued inductors with a larger volume. For instance, the Sumida CR43 series, in values ranging from 3.3µH to, will give a A application a few percentage points increase in efficiency. CAPACITOR SELECTION Low ESR (equivalent series resistance) capacitors should be used at the output to minimize the output ripple voltage. Multilayer ceramic capacitors are an excellent choice, as they have an extremely low ESR and are available in very small packages. X5R dielectrics are preferred, followed by X7R, as these materials retain their capacitance over wide voltage and temperature ranges. A µf to 22µF output capacitor is sufficient for most applications while a to µf capacitor will suffice for the A. Solid tantalum or OS-CON capacitors can be used, but they will occupy more board area than a ceramic and will have a higher ESR. Always use a capacitor with a sufficient voltage rating. Ceramic capacitors also make a good choice for the input decoupling capacitor, which should be placed as close as possible to the /A. A to input capacitor is sufficient for most applications. Table 3 shows a list of several ceramic capacitor manufacturers. Consult the manufacturers for detailed information on their entire selection of ceramic parts. Table 3. Ceramic Capacitor Manufacturers Taiyo Yuden (48) AVX (83) Murata (74) The decision to use either low ESR (ceramic) capacitors or the higher ESR (tantalum or OS-CON) capacitors can effect the stability of the overall system. The ESR of any capacitor, along with the capacitance itself, contributes a zero to the system. For the tantalum and OS-CON capacitors, this zero is located at a lower frequency due to the higher value of the ESR, while the zero of a ceramic capacitor is at a much higher frequency and can generally be ignored. A phase lead zero can be intentionally introduced by placing a capacitor () in parallel with the resistor () between and V as shown in Figure. The frequency of the zero is determined by the following equation. ƒ Z = 2 π By choosing the appropriate values for the resistor and capacitor, the zero frequency can be designed to improve the phase margin of the overall converter. The typical target value for the zero frequency is between 2kHz to 6kHz. Figure 3 shows the transient response of the inverting converter from Figure without the phase lead capacitor. The phase margin is reduced as evidenced by more ringing in both the output voltage and inductor current. A 22pF capacitor for results in better phase margin, which is revealed in Figure 4 as a more damped response and less overshoot. Figure 5 shows the transient response when a 22µF tantalum capacitor with no phase lead capacitor is used on the output. The higher output voltage ripple is revealed in the upper waveform as a thicker line. The transient response is adequate which implies that the ESR zero is improving the phase margin. 2mV/DIV AC COPLED I LA + I LB.5A/DIV AC COPLED LOAD CRRENT 2mA ma µs/div 93 F3 Figure 3. Transient Response of Inverting Converter Without Phase Lead Capacitor 6

7 /A APPLICATIO S I FOR ATIO W 2mV/DIV AC COPLED 2V/DIV I LA + I LB.5A/DIV AC COPLED LOAD CRRENT 2mA ma µs/div 93 F4 Figure 4. Transient Response of Inverting Converter with 22pF Phase Lead Capacitor.V/DIV AC COPLED I LA + I LB.5A/DIV AC COPLED LOAD CRRENT 2mA ma 5µs/DIV 93 F5 Figure 5. Transient Response of Inverting Converter with 22µF Tantalum Output Capacitor and No Phase Lead Capacitor START-P/SOFT-START For most /A applications, the start-up inrush current can be high. This is an inherent feature of switching regulators in general since the feedback loop is saturated due to being far from its final value. The I IN.5A/DIV AC COPLED V V 5µs/DIV 93 F6 Figure 6. Start-p Waveforms for to Application (Figure ). No Soft-Start Circuit. Reaches in 5µs; Input Current Peaks at 8mA regulator tries to charge up the output capacitor as quickly as possible, which results in a large inrush current. Figure 6 shows a typical oscillograph of the start-up waveform for the application of Figure starting into a load of 33Ω. The lower waveform shows being pulsed from V to. The middle waveform shows the input current, which reaches as high as.8a. The total time required for the output to reach its final value is approximately 5µs. For some applications, this initial inrush current may not be acceptable. If a longer start-up time is acceptable, a soft-start circuit consisting of R SS and C SS, as shown in Figure 7, can be used to limit inrush current to a lower value. Figure 8 shows the relevant waveforms with R SS = 5k and C SS = 33nF. Input current, measured at, is limited to a peak value of.5a as the time required to reach final value increases to ms. In Figure 9, C SS is CRRENT PROBE LA LB V SS R SS 5k D2 N448 C SS 33nF/68nF + SW 29.4k k : TAIYO YDEN X5R JMK22BJ475MG : TAIYO YDEN X5R LMK22BJ5MG : TAIYO YDEN XR5 JMK325BJ226MM : ON SEMICONDCTOR MBR52 L: SMIDA CLS62-22pF 22µF 93 F7 Figure 7. R SS and C SS at Pin Provide Soft-Start to Inverting Converter 7

8 /A APPLICATIO S I FOR ATIO 2V/DIV I IN.5A/DIV AC COPLED V SS V 2µs/DIV 93 F8 Figure 8. R SS = 5k, C SS = 33nF; Reaches in ms; Input Current Peaks at 5mA 2V/DIV I IN.5A/DIV AC COPLED V SS V W 5µs/DIV 93 F9 Figure 9. R SS = 5k, C SS = 68nF; Reaches in.6ms; Input Current Peaks at 35mA increased to 68nF, resulting in a lower peak input current of 35mA with a ramp time of.6ms. C SS or R SS can be increased further for an even slower ramp, if desired. Diode D2 serves to quickly discharge C SS when V SS is driven low to shut down the device. D2 can be omitted, resulting in a soft-stop slow discharge of the output capacitor. DIODE SELECTION A Schottky diode is recommended for use with the / A. The Motorola MBR52 is a very good choice. Where the input to output voltage differential exceeds 2V, use the MBR53 (a 3V diode). These diodes are rated to handle an average forward current of.5 A. In applications where the average forward current of the diode exceeds.5a, a Microsemi PS587 rated at A is recommended. LAYOT HINTS The high-speed operation of the /A demands careful attention to board layout. You will not get advertised performance with careless layout. Figure shows the recommended component placement. The ground cut at the cathode of is essential for low noise operation. + LB LA F SHTDOWN Figure. Suggested Component Placement. Note Cut in Ground Copper at s Cathode 8

9 /A TYPICAL APPLICATIO S to 2V Inverting Converter Efficiency LA SW 84.5k k LB 2V 5mA µf EFFICIENCY (%) : TAIYO YDEN X5R JMK22BJ475MG : TAIYO YDEN X5R TMK36BJ5ML : TAIYO YDEN X5R EMK325BJ6MM : ON SEMICONDCTOR MBR52 L: SMIDA CLS62-93 TA LOAD CRRENT (ma) TA3 5 to Inverting Converter sing ncoupled Inductors L L2 SW 29.4k k 22pF 3mA 22µF : TAIYO YDEN X5R JMK22BJ475MG : TAIYO YDEN X5R LMK22BJ5MG : TAIYO YDEN X5R JMK22BJ226MM : ON SEMICONDCTOR MBR52 L, L2: MRATA LQH3K4 93 TA4 2.2MHz, to Inverting Converter Efficiency L 4.7µH L2 4.7µH 8 75 SW A 28.7k k 8pF 3mA EFFICIENCY (%) : TAIYO YDEN X5R JMK22BJ475MG : TAIYO YDEN X5R LMK22BJ5MG : TAIYO YDEN X5R JMK22BJ475MG : ON SEMICONDCTOR MBR52 L, L2: MRATA LQH3R7M24 93 TA5a LOAD CRRENT (ma) 93 TA5b 9

10 /A TYPICAL APPLICATIO S 2.2MHz, to Converter ses Tiny Chip Inductors Efficiency L 3.3µH L2 3.3µH µF SW A 28.7k k 68pF 2mA EFFICIENCY (%) : TAIYO YDEN X5R JMK22BJ225MG : TAIYO YDEN X5R LMK22BJ5MG : TAIYO YDEN X5R JMK22BJ475MG : ON SEMICONDCTOR MBR52 L, L2: PANASONIC ELJPR3MF 93 TA6a LOAD CRRENT (ma) 93 TA6b SLIC Power Supply with 33V and 68V Outputs, ses Soft-Start 2V 6V V SS R SS 5k L 22µH C SS 68nF SW k Ω R3 25.5k C6 pf R4 2.7k *TOTAL OTPT POWER NOT TO EXCEED 3.3W TO C5: X5R OR X7R, D2: BAV99 OR EQIVALENT L: SMIDA CR D C TA8 COM 33V ma* 2 66V 48mA*

11 /A TYPICAL APPLICATIO S SLIC Power Supply with 2.6V and 6 Outputs, ses Soft-Start V SS R SS 5k C SS 68nF 6V L SW k Ω R3 6.2k C8 pf *TOTAL OTPT POWER NOT TO EXCEED.3W TO C7: X5R OR X7R, D2: BAV99 OR EQIVALENT L: SMIDA CR43- R4 2.7k D2 3 2 D3 3 2 C5 2 C6 2 C TA9 COM 2.6V 48mA* 2 6 2mA* PACKAGE DESCRIPTIO S5 Package 5-Lead Plastic TSOT-23 (Reference LTC DWG # ).62 MAX.95 REF 2.9 BSC (NOTE 4).22 REF 3.85 MAX 2.62 REF.4 MIN 2.8 BSC.5.75 (NOTE 4) PIN ONE RECOMMENDED SOLDER PAD LAYOT PER IPC CALCLATOR.95 BSC.3.45 TYP 5 PLCS (NOTE 3) BSC DATM A. MAX REF.9.2 NOTE: (NOTE 3). DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLSIVE OF PLATING 4. DIMENSIONS ARE EXCLSIVE OF MOLD FLASH AND METAL BRR 5. MOLD FLASH SHALL NOT EXCEED.254mm 6. JEDEC PACKAGE REFERENCE IS MO-93.9 BSC S5 TSOT REV B Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.

12 /A TYPICAL APPLICATIO 2.2MHz, 2V to Converter ses Low Profile Coupled Inductor 2V LA 4.7µH. LB 4.7µH 2.2µF SW A 28.7k k 45mA : TAIYO YDEN Y EMK22F225ZG :. 2 X5R : TAIYO YDEN X5R JMK22BJ475MG : ON SEMICONDCTOR MBR52 L: SMIDA CLQ4-4R7 DRAWING #5382-T39 93 TA7a Efficiency 8 75 EFFICIENCY (%) LOAD CRRENT (ma) 93 TA7b 5 RELATED PARTS PART NMBER DESCRIPTION COMMENTS LT37 Single Cell Micropower 6kHz PWM DC/DC Converter 3.3V at 75mA from One Cell, MSOP Package LT36 Burst Mode TM Operation DC/DC with Programmable Current Limit. Minimum, Precise Control of Peak Current Limit LT37 2-Cell Micropower DC/DC with Low-Battery Detector 3.3V at 2mA from Two Cells, 6kHz Fixed Frequency LT6 Single Cell Micropower DC/DC Converter 3V at 3mA from V,.7MHz Fixed Frequency LT6 Inverting.4MHz Switching Regulator in 5-Lead ThinSOT at 5mA from Input. Tiny SOT-23 Package LT63.4MHz Switching Regulator in 5-Lead ThinSOT at 2mA from 3.3V Input. Tiny SOT-23 Package LT65 Micropower Constant Off-Time DC/DC Converter in 5-Lead ThinSOT 2V at 2mA from 2.. Tiny SOT-23 Package LT67 Micropower Inverting DC/DC Converter in 5-Lead ThinSOT at 2mA from 2.. Tiny SOT-23 Package LT93/LT93A.2MHz/2.2MHz, A Switching Regulators in 5-Lead ThinSOT at 45mA from 3.3V Input. Tiny SOT-23 Package Burst Mode operation is a trademark of Linear Technology Corporation. 2 Linear Technology Corporation 63 McCarthy Blvd., Milpitas, CA (48)432-9 FAX: (48) LT/LT 5 REV A PRINTED IN SA LINEAR TECHNOLOGY CORPORATION 2

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